Post on 19-Oct-2020
transcript
1
CIRFCircuit Intégré Radio Fréquence
Lecture I
•Introduction•Baseband Pulse Transmission•Digital Passband Transmission•Circuit Non-idealities Effect
Hassan AboushadyUniversité Paris VI
CIRFCircuit Intégré Radio Fréquence
Lecture I
•Introduction•Baseband Pulse Transmission•Digital Passband Transmission•Circuit Non-idealities Effect
Hassan AboushadyUniversité Paris VI
M.H. Perrott MIT OCW M.H. Perrott MIT OCW
2
M.H. Perrott MIT OCW M.H. Perrott MIT OCW
M.H. Perrott MIT OCW
Multidisciplinarity of radio design
H. Aboushady University of Paris VI
3
• S. Haykin, “Communication Systems”, Wiley 1994.
• B. Razavi, “RF Microelectronics”, Prentice Hall, 1997.
• M. Perrott, “High Speed Communication Circuits and
Systems”, M.I.T.OpenCourseWare, http://ocw.mit.edu/,
Massachusetts Institute of Technology, 2003.
• D. Yee, “ A Design methodology for highly-integrated
low-power receivers for wireless communications”,
http://bwrc.eecs.berkeley.edu/, Ph.D. University of
California at berkeley, 2001.
References
H. Aboushady University of Paris VI
CIRFCircuit Intégré Radio Fréquence
Lecture I
•Introduction•Baseband Pulse Transmission•Digital Passband Transmission•Circuit Non-idealities Effect
Hassan AboushadyUniversity of Paris VI
H. Aboushady University of Paris VI
Digital Baseband Transmission
ISI : InterSymbol Interference
Channel Noise
Detecting a pulse transmitted over a channel that is corrupted by additive noise.
The result of data transmission over a non-ideal channel is that each received pulse is affected by adjacent pulses.
Major sources of errors in the detection of transmitted digital data:
H. Aboushady University of Paris VI
Matched Filter
Linear Receiver Model
• Filter Requirements, h(t) :• Make the instantaneous power in the output signal g0(t) , measured at time t=T, as large as possible compared with the average power of the output noise, n(t).
)()()( 0 tntgty +=Tttwtgtx ≤≤+= 0,)()()( )(th
• g(t) : transmitted pulse signal, binary symbol ‘1’ or ‘0’.• w(t) : channel noise, sample function of a white noise process of zero mean and power spectral density N0/2.
4
H. Aboushady University of Paris VI
Matched Filter for Rectangular Pulse
)()( tTgkthopt −=
g(t)
T
g(t)
tT
h(t) = g(T-t)
tT
g(-t)
t
h(t) for a rectangular Pulse:
Filter Output g(t)*h(t):
Implementation:
H. Aboushady University of Paris VI
Error Rate due to Noise
In the interval , the received signal:bTt ≤≤0
+−++
=sent was'0' symbol,)(
sent was'1' symbol,)()(
twA
twAtx
Tb is the bit duration, A is the transmitted pulse amplitude
• The receiver has prior knowledge of the pulse shape but not its polarity.
• There are two possible kinds of error to be considered:(1) Symbol ‘1’ is chosen when a ‘0’ was transmitted.(2) Symbol ‘0’ is chosen when a ‘1’ was transmitted.
x(t)
H. Aboushady University of Paris VI
PDF: Probability Density Function
Normalized PDF µµµµY= 0 and σσσσY=1
−−=2
2
2
)(exp
2
1)(
Y
Y
Y
Y
yyf
σµ
πσ
• Gaussian Distribution:
• Symbol ‘0’ was sent:
dyyf
yPP
Y
e
∫∞
=
>=
λ
λ
)0(
sent) was'0' symbol(0
b
YY T
NA
2, 02 =−= σµ
• Symbol ‘1’ was sent:
dyyf
yPP
Y
e
∫∞−
=
<=λ
λ
)1(
sent) was'1' symbol(0
b
YY T
NA
2, 02 =+= σµ
H. Aboushady University of Paris VI
BER in a PCM receiver
1100 eee PpPpP +=
10 ee PP =
2
110 == pp
10 eee PPP ==
=
02
1
N
EerfcP b
e
5
CIRFCircuit Intégré Radio Fréquence
Lecture I
•Introduction•Baseband Pulse Transmission•Digital Bandpass Transmission•Circuit Non-idealities Effect
Hassan AboushadyUniversité Paris VI
• In wired systems, coaxial lines exhibit superior shielding
at higher frequencies
• In wireless systems, the antenna size should be a
significant fraction of the wavelength to achieve a
reasonable gain.
• Communication must occur in a certain part of the
spectrum because of FCC regulations.
• Modulation allows simpler detection at the receive end in
the presence of non-idealities in the communication
channel.
Why Modulation?
H. Aboushady University of Paris VI
• mi : one symbol every T seconds
• Symbols belong to an alphabet of M symbols: m1, m2, …, mM
MmPp
mPmPmP
ii
M
1)(
)(...)()( 21
==
===• Message output probability:
• Example: Quaternary PCM, 4 symbols: 00, 01, 10, 11
H. Aboushady University of Paris VI
Message Source
MidttsET
ii ...,,2,1,)(0
2 == ∫• Energy of si(t) :
H. Aboushady University of Paris VI
Transmitter
• Signal Transmission Encoder: produces a vector si made up of Nreal elements, where N M .• Modulator: constructs a distinct signal si(t) representing mi of duration T .
≤
• si(t) is real valued and transmitted every T seconds.
6
Examples of Transmitted signals: si(t)
H. Aboushady University of Paris VI
• The modulator performs a step change in the amplitude, phase or frequency of the sinusoidal carrier
• ASK: Amplitude Shift Keying
• PSK: Phase Shift Keying
• FSK: Frequency Shift Keying
Special case: Symbol Duration T = Bit Duration, Tb
=≤≤
+=Mi
Tttwtstx i ,...,2,1
0),()()(
• Received signal x(t) :
H. Aboushady University of Paris VI
Communication Channel
• Two Assumptions:•The channel is linear (no distortion).• si(t) is perturbed by an Additive, zero-mean, stationnary, White, Gaussian Noise process (AWGN).
H. Aboushady University of Paris VI
Receiver
m̂
•TASK: observe received signal, x(t), for a duration T and make a best estimate of transmitted symbol, mi .
•Detector: produces observation vector x . •Signal Transmission Decoder: estimates using x, the modulation format and P(mi) .
• The requirement is to design a receiver so as to minimize the average probability of symbol error:
∑=
≠=M
iiie mPmmPP
1
)()ˆ(
H. Aboushady University of Paris VI
Coherent and Non-Coherent Detection
• Coherent Detection: - The receiver is time synchronized with the transmitter.- The receiver knows the instants of time when the modulator changes state.- The receiver is phase-locked to the transmitter.
• Non-Coherent Detection:- No phase synchronism between transmitter and receiver.
7
H. Aboushady University of Paris VI
Coherent Binary PSK:
b
T
Edtttssb
== ∫ )()( 1
0
111 φ
• M=2, N=1
• One basis function:
• Signal constellation consists of two message points:
)2cos(2
)(1 tfT
Ets c
b
b π= )2cos(2
)(2 ππ += tfT
Ets c
b
b
bTt ≤≤0
• To ensure that each transmitted bit contains an integral number of cycles of the carrier wave, fc =nc/Tb, for some fixed integer nc.
bc
b
TttfT
t ≤≤= 0,)2cos(2
)(1 πφ
b
T
Edtttssb
−== ∫ )()( 1
0
221 φ
H. Aboushady University of Paris VI
Generation and Detection of Coherent Binary PSK
• Assuming white Gaussian Noise with PSD = N0/2 ,
The Bit Error Rate for coherent binary PSK is:
=
02
1
N
EerfcP b
e
Binary PSK Transmitter
Coherent Binary PSK Receiver
H. Aboushady University of Paris VI
Coherent QPSK:
• M=4, N=2:
• Two basis function:
≤≤
−+=elsewhere , 0
0,4
)12(2cos2
)( TtitfT
Ets c
i
ππ
)4
2cos(2
)(1
ππ += tfT
Ets c
TttfT
t c ≤≤= 0,)2cos(2
)(1 πφ
TttfT
t c ≤≤= 0,)2sin(2
)(2 πφ
)4
32cos(2
)(2
ππ += tfT
Ets c
)4
52cos(2
)(3
ππ += tfT
Ets c
)4
72cos(2
)(4
ππ += tfT
Ets c
H. Aboushady University of Paris VI
Constellation Diagram of Coherent QPSK System
=
0
2/
2
1
N
EerfcPe
=
02
1
N
EerfcP b
e
• Assuming AWGN with PSD = N0/2 ,The Bit Error Rate for coherent QPSK is:
with E = 2 Eb
Identical to BPSK
8
H. Aboushady University of Paris VI
QPSK waveform: 01101000
H. Aboushady University of Paris VI
Generation and Detection of Coherent QPSK Signals
QPSK Transmitter
Coherent QPSK Receiver
H. Aboushady University of Paris VI
Power Spectra of BPSK ,QPSK and M-ary PSK
QPSK
BPSK
8-PSK
• Symbol Duration: MTT b 2log=
• Power Spectral Density of an M-ary PSK signal: )log(sinclog2
)(sinc2)(
22
2
2
MfTME
TfEfS
bb
B
=
=
)(sinc2)( 2 fTEfS bbB =
)2(sinc4)( 2 fTEfS bbB =
)3(sinc6)( 2 fTEfS bbB =
CIRFCircuit Intégré Radio Fréquence
Lecture I
•Introduction•Baseband Pulse Transmission•Digital Passband Transmission•Circuit Non-idealities Effect
Hassan AboushadyUniversité Paris VI
9
Binary Dataantenna
011011Multiplexer
Decision Device
Threshold = 0
Threshold = 0
Decision Device
T
T
path I
path Q
∫T
dt0
∫T
dt0
)2cos(2
)(1 tfT
t cπφ =
)2sin(2
)(1 tfT
t cπφ =
I
Q
QPSK Constellation Diagram
00 10
1101
H. Aboushady University of Paris VI
QPSK Receiver
Circuit Noise (Thermal, 1/f)
Gain Mismatch
Phase Mismatch
DC Offset
Frequency Offset
Local Oscillator phase noise
H. Aboushady University of Paris VI
Receiver Circuit Non-Idealities
Circuit Noise:
• Thermal Noise• Resistors• Transistors
• Flicker (1/f) Noise• MOS transistors
I
Q
H. Aboushady University of Paris VI
Circuit Noise
-2 -1.5 -1 -0.5 0 0.5 1 1.5 2-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
Q
I
A(1-α/2)
A(1+α/2)
H. Aboushady University of Paris VI
Gain Mismatch
10
-2 -1.5 -1 -0.5 0 0.5 1 1.5 2-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
Q
I
H. Aboushady University of Paris VI
Phase Mismatch
offset
offset
I
Q
-2 -1.5 -1 -0.5 0 0.5 1 1.5 2-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
Q
I
H. Aboushady University of Paris VI
DC Offset
-2 -1.5 -1 -0.5 0 0.5 1 1.5 2-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
Q
I
H. Aboushady University of Paris VI
Frequency Offset
H. Aboushady University of Paris VI
Local Oscillator Phase Noise
11
H. Aboushady University of Paris VI
Reciprocal Mixing
CIRFCircuit Intégré Radio Fréquence
Lecture II
•Introduction•Negative Resistance Oscillators•Integrated Passive Components•Phase Noise in Local Oscillators
Hassan AboushadyUniversity of Paris VI
CIRFCircuit Intégré Radio Fréquence
Lecture II
•Introduction•Negative Resistance Oscillators•Integrated Passive Components•Phase Noise in Local Oscillators
Hassan AboushadyUniversity of Paris VI
• M. Perrott, “High Speed Communication Circuits and
Systems”, M.I.T. OpenCourseWare, http://ocw.mit.edu/,
Massachusetts Institute of Technology, 2003.
• T. Lee, “The Design of CMOS Radio-Frequency Integrated
Circuits”, Cambridge University Press, 2004.
• B. Razavi, “Design of Analog CMOS Integrated Circuits”,
Mc Graw-Hill, 2001.
References
H. Aboushady University of Paris VI
12
Binary Dataantenna
011011Multiplexer
Decision Device
Threshold = 0
Threshold = 0
Decision Device
T
T
path I
path Q
∫T
dt0
∫T
dt0
)2cos(2
)(1 tfT
t cπφ =
)2sin(2
)(2 tfT
t cπφ =
I
Q
QPSK Constellation Diagram
00 10
1101
H. Aboushady University of Paris VI
QPSK Receiver
13
CIRFCircuit Intégré Radio Fréquence
Lecture II
•Introduction•Negative Resistance Oscillators•Integrated Passive Components•Phase Noise in Local Oscillators
Hassan AboushadyUniversity of Paris VI
14
15
16
17
18
CIRFCircuit Intégré Radio Fréquence
Lecture II
•Introduction•Negative Resistance Oscillators•Integrated Passive Components•Phase Noise in Local Oscillators
Hassan AboushadyUniversity of Paris VI
19
20
Vertical Metal Capacitors
H. Aboushady University of Paris VI
Lateral Metal Capacitors
H. Aboushady University of Paris VI
Vertical Mesh Metal Capacitors
K.T. Christensen,”Low Power RF Filtering for CMOS Transceivers”, Ph.D. Denmark Technical
University, 2001, http://phd.dtv.dk/2001/oersted/k_t_christensen.pdf
21
22
s
CIRFCircuit Intégré Radio Fréquence
Lecture II
•Introduction•Negative Resistance Oscillators•Integrated Passive Components•Phase Noise in Local Oscillators
Hassan AboushadyUniversity of Paris VI
23
Binary Dataantenna
011011Multiplexer
Decision Device
Threshold = 0
Threshold = 0
Decision Device
T
T
path I
path Q
∫T
dt0
∫T
dt0
)2cos(2
)(1 tfT
t cπφ =
)2sin(2
)(2 tfT
t cπφ =
I
Q
QPSK Constellation Diagram
00 10
1101
H. Aboushady University of Paris VI
QPSK Receiver
H. Aboushady University of Paris VI
Local Oscillator Phase Noise
H. Aboushady University of Paris VI
Reciprocal Mixing Phase Noise in Oscillators
H. Aboushady University of Paris VI
24
25
26
27
28