Adaptive Compensation of Reactive Power

8/13/2019 Adaptive Compensation of Reactive Power

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IEEE TRANSACTIONS ON INDUSTRY APPLICATIONS, VOL. 44, NO. 3, MAY/JUNE 2008 867

Adaptive Compensation of Reactive PowerWith Shunt Active Power Filters

Lucian Asiminoaei,Member, IEEE, Frede Blaabjerg,Fellow, IEEE, Steffan Hansen,Member, IEEE,and Paul Thgersen,Senior Member, IEEE

AbstractThis paper describes an adaptive method for com-pensating the reactive power with an active power filter (APF),which is initially rated for mitigation of only the harmonic cur-rents given by a nonlinear industrial load. It is proven that, ifthe harmonic currents do not load the APF at the rated power,the available power can be used to provide a part of the requiredreactive power. Different indicators for designing such applicationare given, and it is proven that the proposed adaptive algorithmrepresents an added value to the APF. The algorithm is practicallyvalidated on a laboratory setup with a 7-kVA APF.

Index TermsActive filters, harmonics analysis, power-systemharmonic, pulsewidth-modulated inverters, reactive power.

I. INTRODUCTION

SHUNT active power filters (APFs) are solutions used for

compensation of harmonic currents from nonlinear loads.

They can be connected either as a local harmonic-mitigation

solution, next to a given nonlinear load, or as a global solution

at the point of the common coupling (PCC) [1], as it is shown

in Fig. 1. Usually, the optimum location is selected based

on desired performance, network stability, harmonic-mitigation

efficiency, and costs.

The APF detects the harmonic spectrum of the load currentand generates an output current, which ideally is of the same

harmonic spectrum as of the load current but in opposite phase.

In this way, the APF cancels out the harmonic currents and

leaves the fundamental current component to be provided by

the power system [2].

In the last decade, the use of active techniques to mitigate

harmonics has become more attractive due to the technologi-

cal progress in switching power devices, sensors, transducers,

DSPs, and control algorithms [3]. These factors allowed the

implementation of APFs not only in laboratory conditions but

also in real-life applications.

Paper IPCSD-07-101, presented at the 2006 Industry Applications SocietyAnnual Meeting, Tampa, FL, October 812, and approved for publication inthe IEEE TRANSACTIONS ON INDUSTRY APPLICATIONS by the IndustrialPower Converter Committee of the IEEE Industry Applications Society. Man-uscript submitted for review December 23, 2006 and released for publicationOctober 19, 2007.

L. Asiminoaei and S. Hansen are with Danfoss Drives A/S, 6300 Graasten,Denmark (e-mail: [email protected]; [email protected]).

F. Blaabjerg is with the Faculty of Engineering, Science and Medicine,Aalborg University, 9220 Aalborg, Denmark (e-mail: [email protected]).

P. Thgersen is with KK-Electronic A/S, 7400 Herning, Denmark (e-mail:[email protected]).

Digital Object Identifier 10.1109/TIA.2008.921366

The efficiency of an APF is higher than as of a shunt

passive filter, because the real power consumed by the APF

is much smaller. Unlike the shunt passive filters, there is no

need of connecting multiple branches for mitigation of several

harmonic orders at once.

One single APF is capable of mitigating up to a practical

30th50th harmonic order, meeting the actual harmonic stan-

dards and regulations.

Furthermore, the APFs can protect themselves against volt-

age imbalance and predistortion and keep the same good qualityof the compensated harmonic current. The harmonic compen-

sation with APF is expected typically 5%7% total harmonic

distortion (THDi), while, with a passive filter, the THDi iswithin 10%15%.

However, the costs involved (i.e., equipment, installation,

maintenance) of an APF are higher as compared to typical

passive filters [4].

To minimize the cost and retrofit existing passive-power-

filter installations, various types of hybrid topologies were

introduced and successfully implemented in recent years [17].

The hybrid filters mitigate the harmonic currents relatively well,

and their cost is reduced as compared to a pure active-filter

solution because of lower power-inverter rating. In spite of allthese advantages, the hybrid filter is suitable for applications

where there is a need of reactive-power compensation, just like

in the case of the passive filter. The amount of reactive power

is fixed from design stage according to the maximum demand

and difficult to control, because it depends on the installed

capacitors. For adjustable speed drives (ASDs) based on front-

end diode rectifier, the current displacement is close to unity;

therefore, the use of hybrid filters is of a little interest because

of the risk of generating leading power factor.

In order to increase the value proposition of an APF with-

out changing its design, one may further develop the control,

including more features in terms of power-quality regula-tion, such as compensation of voltage unbalance, dips, swells,

flickers, and damping network resonances. Nevertheless, any of

the above increases even more the cost of harmonic mitigation,

because the APFs inverter must carry a higher power. This

means an increase of the inverter-power capability (insulated-

gate bipolar transistors (IGBTs), the size of the boost LCL

filter, heat-sink, ventilation) but also a larger dc-link for energy

storage.

Reactive-power compensation is another solution to increase

the value proposition of an APF [5]. However, in real applica-

tions, the mitigation of the reactive power with an APF is not

a simple task, because the reactive power may be much higher

0093-9994/$25.00 2008 IEEE


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868 IEEE TRANSACTIONS ON INDUSTRY APPLICATIONS, VOL. 44, NO. 3, MAY/JUNE 2008

Fig. 1. General block diagram of a shunt APF connected at the PCC of an industrial plant.

than the harmonic power, and thus, the APF looses its initial

purpose, again with the same consequence of an increasing cost.

Nevertheless, the mitigation of the reactive power is attractive,as this can be done without increasing the size of the dc

capacitor. Furthermore, reducing the reactive power together

with a reduction in harmonic currents provides higher power

factor, which consequently lowers the losses and improves

network stability.

This paper describes a new adaptive compensation algorithm

of reactive power to utilize the power inverter at maximum. The

proposed algorithm requires no hardware changes or increase

of the power rating. The APF is rated, according to the initial

design specifications, for mitigation of the harmonic currents

at full-loading conditions of a given industrial plant. When the

loading becomes lower and the harmonic currents do not loadthe APF inverter at its full capability, then the reactive power is

compensated within the inverter limits [6].

A similar approach to adaptive compensation of reactive

power is described in [7], where the calculation is based on

empirical coefficients determined and readjusted as a result of

experimental results. Further work of [8] and [9] uses neural

networks to find optimal compensation of harmonic current dis-

tortion and power factor via constrained optimization problem,

based on simulations.

This paper describes an adaptive compensation algorithm

in synchronous dq-frame, thus accommodating an easy im-plementation that retrofits the existing hardware and control

of an APF. This paper proposes three methods of detecting

the available power left for reactive power compensation and

presents the underlying principle. The methods are modeled

with circuit simulators, and the most suitable one is validated

in practice. Several design steps are presented with respect to

the APFs inverter. The proposed algorithms are sustained by

practical measurements on a laboratory setup with a total rated

power of 7 kVA at 400 V.

II. POWERR ATING OFS HUNT A PF

A common characteristic of ASD applications is the

operation at a loading lower then nominal output power, withan average between 70%80%. Although it is expected that

Fig. 2. Decomposition of the total apparent powerSin three power vectors:P1 is the real fundamental power; Q1 is the reactive fundamental power; and

DN is the harmonic-distortion power.

ASD reaches the nominal power, this is not a permanent state.

Otherwise, if the motor needs to operate at full power all the

time, the ASD is not required.

When the ASD loading decreases the harmonic currents are

reduced as well, which leaves the APF operating at a lower

power than it is designed. This opens the possibility of using

the APF for reactive-power compensation, as it is described in

Section I. Typical applications are as follows:

ASD applications (i.e., water pumps, heaters, elevators,

etc.) running at a power lower than nominal;

front-end thyristors-control ASDs, where both harmonic

and reactive currents change with the firing angle;

mixed linear and nonlinear loads, connected together at

the same PCC but operating independently from each

other.

The apparent power Sof the plant shown in Fig. 1 is givenby three power vectors, as shown in Fig. 2

S=

P21 +Q21+D

2N. (1)

An active filter installed at the PCC ideally compensates theentire amount of harmonic distortion power DN. Assuming


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ASIMINOAEI et al.: ADAPTIVE COMPENSATION OF REACTIVE POWER WITH SHUNT ACTIVE POWER FILTERS 869

Fig. 3. Simulation of a front-end diode rectifier adjustable speed drive as a function of loading and the line impedanceLac. (a) Line current THDi. (b) Generatedharmonic power.

sinusoidal voltages, the harmonic-distortion power is calcu-

lated as

DN =SASD THDi (2)

where theSASDand THDiare the apparent power respective ofthe THD from an ASD.

Variation of the THDi with the ASD loading is simulated

in Fig. 3 for a typical three-phase diode-rectifier ASD as a

function of the front-line ac inductance Lac. The results indicatethat if the ASD loading decreases, then the THDi increases,

because the fundamental current becomes smaller. However,the harmonic-distortion power DN is reduced, because theapparent power drawn by ASD is lower. This indicates that the

APF is not used all the time at the full inverter capacity when

the ASD operates in a point lower than nominal. Fig. 3(b) shows

how the distorted power decreases almost linear with the ASD

loading.

If the APF is imposed to compensate both reactive and

harmonic powers, the total rated power of the APF inverter

becomes

SAPF=Q2LIN+D2N (3)SAPF=

(SLIN sin(LIN))

2 + (SASD THDi)2 (4)

SAPFSASD

=

SLINSASD

sin(LIN)2

+ (THDi)21 + (THDi)2

(5)

whereQLIN andLIN are the total reactive power, respectiveof the displacement angle given by the linear loads, DN is theharmonic-distortion power from the nonlinear load associated

with the existing THDi.

One particular case of (5) often quoted in literature [10] is of

a plant consisting of ASDs only but no linear loads, i.e., SLIN=SASD, which gives (6).

Fig. 4. Rating an APF as a function of the existing harmonic current distortionfrom the ASD. A possible case is shown with a value of the THD i lower thanthe designed limit. Thus, the remaining available power of the APF may be usedfor reactive power compensation.

Fig. 4 shows a graphical representation of (6) for different

THDivalues and displacement anglescos(). Fig. 4 shows anexample of an APF which is rated to compensate the maxi-

mum harmonic-distortion power of 50% THDi. For a smaller

THDi, for instance 30% (caused by reduced ASD loading), theAPF mitigates the entire distorted power without reaching the

inverter limit

SAPFSASD

=

(sin())2 + (THDi)2

1 + (THDi)2

=

1 cos()2 + (THDi)2

1 + (THDi)2. (6)

As presented in Section I, it is attractive to use the available

power of the APF inverter for reactive-power compensation.

Depending on the amount of the required reactive power, theAPF may provide only partial compensation. In Fig. 4, the


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Fig. 5. Calculation of the APF rating based on the existingcos(LIN)and total power SLINas in (5). The ratio SLIN/SASDis equal to (a) 0.5, (b) 1, and (c) 2.

Fig. 6. Control block diagram of APF in a typicaldq-frame implementation. The proposed algorithm of adaptive compensation of reactive power can be easilyintegrated into the existing control structure.

active filter is allowed to compensate the reactive power only

up to a cos() of 0.94. For lower values of power factor, theAPF is not capable to compensate the required reactive power.

Taking a more general approach of (5) by assuming that the

plant consists of linear loads generating reactive power and

nonlinear loads (i.e., ASDs), Fig. 5 shows three different cases

showing the effect of an increased ratioSLIN/SASD.If the reactive power is larger than harmonic power (i.e.,

SLIN> SASD), the inverter becomes ineffective to cope withthe imposed compensation requirements.

The outcome of this investigation is that mitigation of both,harmonic distortion and the reactive power, is not a straight-

forward task if the behavior of the plant is not exactly known.

For a plant that requires large reactive-power compensation, the

APF inverter is overrated too much as compared to its initial

purpose of harmonic mitigation. Therefore, an adaptive method

for compensating the reactive power within the inverter limits

is the best choice of keeping the same hardware. This extends

the utilization of the inverter and assures that the design of the

APF is decoupled from the exact knowledge of the plant.

III. CONTROLA LGORITHM

The control algorithm is developed in the synchronousdq-reference frame [10]. The input signals(iL, iF, vS), which

are initially achieved in abc-coordinates (stationary referenceframe), are transformed into thedq-rotating reference frame bymeans of the Park transformation

idiq

=

2

3

cos cos(2/3) cos(+2/3)sin sin(2/3) sin(+2/3)

iaib

ic

(7)

where id, iq and ia, ib, ic are the currents in the dq-frame,

respective inabc-frame, and is the reference angle.The frame rotates with the angular speed of fundamentalfrequency, which transforms the fundamental current into dc

component. The harmonic currents in dq-frame are still acsignals but with a shift in frequency, depending on their positive

or negative sequence. The characteristic harmonics 5th and

+7th harmonics are folded on the 6th in dq-frame, 11th,+13th on 12th, etc. Thus, the harmonic-detection method inFig. 6 resumes to remove the dc signal by means of a high-pass

filter (HPF) [2], [11].

The block diagram of the proposed control (Fig. 6) is a typ-

ical implementation of an APF having the current controller in

the inner loop and the voltage controller in the outer loop [12].

The current control is realized in a combined structure with aclassical proportionalintegral (PI) controller for fundamental


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Fig. 8. Examples of two possible cases. (a) APF compensates only the harmonic distorted power. (b) APF compensates also a part of the reactive power. Forboth cases, the resultant current vector current must be lower than the maximum limit of the inverter current iF(max).

Fig. 9. Generalized representation of the dq-frame currents for an APF current controlled with the algorithm of adaptive compensation of reactive power. Threemethods are proposed here to provide low-pass filtering function. (a) RMS-value case. (b) Peak-value case. (c) Maximum-value case.

compensation is not described, although one can find more

details in [18]. The transient represents a change of the ASD

loading from 50% to 80%. This simulated case does not include

the compensation of reactive power (i.e., the adaptive algorithm

is disable) and are given as reference for comparison with the

next simulation case. The power factor before and after the

transient is 0.91, respective 0.93. The THDiof the sum current

ISstays within 4% in both cases, before and after the transient.

The simulation of the active filter employing the adaptive

compensation algorithm is shown in Figs. 11 and 12.

Fig. 11 shows the resultant reactive current references from

each of the proposed methods. As shown, the highest output is

given by the rms-value method, thus creating the highest reac-

tive power (cos() is increased to 0.990.96 in Fig. 12). Thesimulation results are in agreement with Fig. 9 that shows that

the rms-value method is the least limiting method, because the

rms is always smaller than the peak values. The most restrictive

method is the third one, i.e., maximum-value method, because

the highest resultant peak occurring during the window interval

imposes the reactive current reference.

Regarding the results obtained in the case of peak-valuemethod, the reactive current references lies in between.

As shown in Fig. 11, all methods give zero reactive current

reference during the transient. During transients, the APF must

charge the dc capacitor in order to keep the imposed dc-voltage

reference. When the load step goes to higher values, the d-axiscurrent increases to draw more current from the supply. This

increases the real current reference and, overall, the output APF

current. Consequently, the reactive current reference decreases,

eventually reaching the zero limit.

The ripple seen in all reactive current references (Fig. 11)

can be removed either with supplementary low-pass filter or by

increasing the duration of the window Tw. This is a tradeoffbetween quality and speed. Higher ripple in the reactive current

reference means higher disturbance induced in the harmonic

compensation that affects the overall quality of the harmonic

mitigation.

Regarding the selection of the best proposed method for

practical implementation, it is finally a matter of compliance

with the hardware design and specifications. In APF appli-

cations, the ampere requirement of the power switches (e.g.,

IGBTs) is determined by the peak current and not the rms value.

The peak may reach values two to three times higher than therms current. Thus, large IGBTs are required depending on the


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Fig. 10. Simulated waveforms showing the APF capability to mitigate harmonic currents during a transient. The APF does not compensate reactive power.(a) Line current from ASD. (b) Line current from linear load. (c) Compensation current from APF. (d) APF dc voltage. (e) Line current after harmoniccompensation.

Fig. 11. Simulated output from each proposed filtering method, rms-, peak-, and maximum-value cases. Each method gives a different reactive current reference.

load-current behavior. The rms value of the current determines

the inverter rated power, power losses, and consequently, the

size, volume, and cost. However, as a physical unit, the APF

have several hardware limitations (i.e., safe-operation area) due

to the heat dissipation, IP protection classes, ambient temper-

ature, humidity, etc. It is a matter of individual assessment of

each presented method to establish how much the existing APF

stays in the safe-operation area.

As shown in Fig. 9, the rms-value method may overlap the

maximum current limit. If this is in agreement with the hard-

ware specifications of the APF inverter (i.e., the output peak

current is lower than the maximum value of allowed repetitive

peaks in a given period), then this is the best method forimplementation. The advantage is that it provides the highest

reactive current magnitude, therefore, the highest reactive cur-

rent compensation.

The maximum-value method is much more restrictive, which

is suitable for inverters operating at the limit of their ther-

mal design or to assure a higher protection. One concern

is the higher risk of discontinuous reactive current injected

by the APF, which may create oscillations of the network

voltage.

The peak-value method gives higher output reactive cur-

rent as compared to maximum-value method, but it has a

lower risk to overload the inverter as compared to the rms-

value method. The simulations conclude that the peak-value

method is a suitable candidate for further validation by labo-ratory tests.


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Fig. 12. Simulated waveforms of the line current after the harmonic current compensation. The reactive power is also compensated according the proposedmethods. (a) At 50% ASD loading. (b) At 80% ASD loading.

Fig. 13. General diagram of the laboratory setup. The APF compensate the harmonics and the reactive power from the ASD and the RL load.

IV. IMPLEMENTATION

The proposed topology and control method are tested on a

laboratory setup (see Fig. 13), where the APF is realized with a

Danfoss inverter VLT 5006 rated 400 V, 7.6 kVA. The original

control card dedicated for motor control was replaced with a

custom-made control card interfacing the IGBT gate commandsand protections.

The value of the inverter boost inductor is LF= 7 mH,and the dc capacitor is CDC= 2 mF. The switching fre-quency is set to 10.2 kHz. The sampling frequency is iden-

tical to the switching frequency, and the sampling is done

synchronous with the pulsewidth-modulation (PWM) interrupt

routine. The control algorithm is implemented by using the

MATLAB/Simulink real-time workshop toolbox. The imple-mentation is done in a floating-point DSP, although the PWM


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Fig. 14. Measured waveforms during a change in the ASD loading from 50%

to 75%. The APF compensates the harmonic currents and the reactive powerwith the proposed peak-value adaptive compensation method.

generation is executed by TMS320F240, embedded fixed-point

16-b DSP.

The harmonic currents are given by a three-phase diode dc-

smoothed rectifier that replicates the behavior of a typical ASD.

The rectifier is loaded with a variable resistor RLoad in therange of 50200 , which simulates a variable loading. Thesetup is arranged to perform a load step from 50% to 75%.

In parallel with the ASD, there is an RL load with a power

of 3 kVA and cos() of 0.88. The experiment consists of

maintaining the RL constant and changing the ASD loading.The APF is a typical feed-forward topology with a control

loop as described in Section III. The implementation of adaptive

compensation of the reactive power considers the peak-value

algorithm only. The maximum current limit set to 5 A. This

limitation is lower compared to the maximum capability of the

inverter for protection purpose.

The APF reduces the harmonic current distortion from an

existing THDi of 27% down to 2%. The harmonic currents are

controlled as explained in Section III by considering the first

five characteristic pairs, i.e., 5th, 7th, . . ., 31st [18]. The reactivepower is also reduced as much as the current limit allows.

Fig. 14 shows the performance of the APF to compensate thereactive power before, during, and after the transient.

At 50% ASD loading, the APF compensates the entire re-

active power, reaching a displacement angle cos() of 0.99[see IS in Fig. 15(a)]. At 75% ASD loading, the APF cannotcompensate the entire reactive current, because it is prioritized

to provide harmonic compensation at first.

Higher ASD loading means higher harmonic currents, which

in turn demands higher currents in APF. At 75% ASD loading,

the APF provides a lower displacement angle cos() of only0.98 [see IS in Fig. 15(b)] because of reaching the invertercurrent limit.

Fig. 16 shows the evolution of the filter currents in

dq-coordinates (d-axis controls the real current, and q-axiscontrols the reactive current). In both cases (50% and 75%

of the ASD loading), the inverter operates within the same

imposed maximum limit of 5 A. However, the center point (i.e.,

reactive current reference) is lower on q-axis for the case of75% loading, indicating a reduced reactive current reference. It

is interesting to see that the center point on thed-axis is slightlyincreased, which is the effect of higher real current drawn by

the APF. This is because the APF is required to produce higherharmonic content at the output, which determines higher losses,

covered by a higher real current.

V. LIMITATIONSD URINGT RANSIENTS

The APFs control calculates two current references, the

harmonic and reactive currents, of which the total value should

stay within the inverter limits. Therefore, whenever reaching

the maximum current limit, the control must decide which of

the current references should take priority. As presented herein,

the harmonic current reference has priority over the reactive

current. Thus, when the total current reference reached the max-

imum limit, the reactive current reference was reduced to zero.However, the efficiency of this algorithm depends on the

duration and magnitude of the transient. Thus, there are three

possibilities that may occur as follows.

1) The APF controls both reactive and harmonic powers

operating within the limits.

2) The maximum limit is reached but the duration of the

transient is smaller than the window Tw. In this case, thecontrol is able to set the reactive current reference to zero

in useful time, while keeping a proper harmonic current

mitigation.

3) The control is not able to calculate the required current

references fast enough or the magnitude of the imposedreference is over the inverter limit. Thus, both reactive

and harmonic currents are limited to protect the inverter.

In this case, the APF is unable to mitigate the harmonic

currents.

VI. CONCLUSION

This paper describes an adaptive algorithm for reactive-

power compensation for shunt APF. The proposed algorithm

compensates the reactive power if the APF inverter current limit

is not reached. The principle is based on calculation of instan-

taneousd- andq-axes currents to determine by different meansthe average value of reactive current (i.e., q-axis) imposed asreference.

This paper proposes three methods of detecting the available

power left for reactive power compensation, referred to as rms-

value, peak-value, and maximum-value method. The methods

are analyzed and simulated. While it is analyzed that the best

implementation depends on APF hardware design and existing

specifications, it is concluded that a suitable candidate for

practical implementation is the peak-value method. This is

because the peak-value method gives higher reactive current

as compared to the maximum-value method but lower risk

to overload the APF inverter as compared to the rms-value

method. This method is further tested on an existing laboratorystand rated as 7 kVA, 400 V, delivering the expected results.


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Fig. 15. Snapshots from measured waveforms in Fig. 14 magnifying the time scale. (a) At 50% ASD loading. (b) At 75% ASD loading.

Fig. 16. Filter current trajectory indq-plane when the APF uses the adap-tive algorithm for reactive-power compensation. While the ASD loading isincreased from 50% to 75%, the APF keeps the total filter current lower thanthe maximum limit.

This paper describes the APF structure and implementation

of the control algorithm in the dq-reference frame. The pro-posed algorithm extends the utilization of the APF inverter and

assures that its design is decoupled from the exact knowledge

of the plant.

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filter topology based on parallel interleaved inverters, IEEE Trans. Ind.Electron., vol. 55, no. 3, pp. 11751189, Mar. 2008.

Lucian Asiminoaei (S03M06) received theM.Sc.E.E. degree from the Faculty of Shipbuildingand Electrical Engineering, Section of Power Elec-tronics and Advanced Control Systems, Dunarea deJos University of Galati, Galati, Romania, in 1997,and the Ph.D. degree from the Institute of EnergyTechnology, Aalborg University, Aalborg, Denmark,in 2006.

From 1996 to 2003, he was a Maintenance En-gineer with Iron&Steelworks Sidex S.A., Galati. In2003, he was with the Institute of Energy Technol-

ogy, Department of Power Electronics and Drives, Aalborg University, wherehe was involved in projects sponsored by Danfoss Drives A/S, Graasten,Denmark, and Power Lynx A/S, Denmark. He was a Visiting Scholar withTexas A&M University, College Station. He is currently with Danfoss DrivesA/S. His areas of interests include harmonic mitigation, harmonic measure-ment, and active filters.

Frede Blaabjerg (S86M88SM97F03) re-ceived the M.Sc.EE. degree from Aalborg Univer-sity, Aalborg, Denmark, in 1987, where he alsoreceived the Ph.D. degree from the Institute of En-ergy Technology in 1995.

From 1987 to 1988, he was with ABBScandia,Randers, Denmark. In 1992, he was an AssistantProfessor, in 1996, an Associate Professor, and in1998, a Full Professor in power electronics anddrives and, since 2006, he has been the Dean of theFaculty of Engineering, Science and Medicine with

Aalborg University. His research areas are in power electronics, static powerconverters, ac drives, switched reluctance drives, modeling, characterizationof power semiconductor devices and simulation, wind turbines, and greenpower inverters. He is the author or coauthor of more than 400 publica-tions in his research fields including the book Control in Power Electronics(Eds. M.P. Kazmierkowski, R. Krishnan, F. Blaabjerg, Academic Press, 2002).He has held a number of chairman positions in research policy and researchfunding bodies in Denmark.

Dr. Blaabjerg was appointed to the board of the Danish High Tech-nolgy Foundation in 2007. He has been an Associate Editor of the IEEETRANSACTIONS ON INDUSTRY APPLICATIONS , IEEE TRANSACTIONS ONPOWER ELECTRONICS, Journal of Power Electronics, and of the Danish

journal Elteknik. Since 2006, he has been the Editor-in-Chief of the IEEETRANSACTIONS ONPOWER ELECTRONICS. He was the recipient of the 1995Angelos Award, for his contribution to modulation technique and control ofelectric drives, and an Annual Teacher Prize from Aalborg University in 1995.In 1998, he was the recipient of the Outstanding Young Power Electronics

Engineer Award from the IEEE Power Electronics Society. He was the recipientof nine IEEE Prize Paper Awards in the last ten years. He was the recipient ofthe C. Y. OConnor Fellowship 2002 from Perth, Australia, the Statoil Prize in2003 for his contributions to power electronics, and the Grundfos Prize in 2004for his contributions to power electronics and drives. From 2005 to 2007, hewas a Distinguished Lecturer for the IEEE Power Electronics Society.

Steffan Hansen (S95A96M99) was born inSonderborg, Denmark, in 1971. He received theM.Sc.E.E. and Ph.D. degree from Aalborg Uni-versity, Aalborg, Denmark, in 1996 and 2001, re-spectively. His Ph.D. degree was supported byan industrial fellowship from Danfoss Drives A/S,Graasten, Denmark, and the Danish Academy ofTechnical Sciences.

He is currently the Director of Technology withDanfoss Drives A/S, where he has been since 1996in various positions. His responsibilities include so-

lutions to reduce line-side harmonics from adjustable-speed drives, controlengineering of adjustable-speed drives, and their applications.

Paul Thgersen (M92SM01) was born in Thy,Denmark, on June 29, 1959. He received theM.Sc.E.E. degree in control engineering and thePh.D. degree in power electronics and drives fromAalborg University, Aalborg, Denmark, in 1984 and1989, respectively.

From 1988 to 1991, he was an Assistant Professorwith Aalborg University. From 1991 to 2005, he waswith Danfoss Drives A/S, Graasten, Denmark, where

he was, first, a Research and Development Engineerand, later, Manager of Technology, mainly responsi-ble for the drives control technology area. Since 2006, he has been the Managerof the Modeling and Control Group, which is a part of the R&D Depart-ment, KK-Electronic A/S, Herning, Denmark. Since 1991, he has had a closerelationship with Aalborg University, resulting in more than 20 coauthoredpapers and participation in more than ten Ph.D. student advisory groups.

Dr. Thgersen was the recipient of the Angelos Award in 1999 for hiscontributions to the development of industrial drives.

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Adaptive Compensation of Reactive Power

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