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    CAD/CAE for Power

    Electronics

    Course no. 2

    Design and modelling aspects of the

    main DC-DC converters

    Content

    1. DC, RMS

    2. Main unidirectional single-stage DC-DC Converters (Design Aspects)

    3. Chopper with R load

    4. Chopper with RLE load

    5. Step-down (buck) converter6. Step-up converter (Boost)

    7. Buck-Boost converter (inverted voltage)

    8. Flyback converter (isolated buck-boost converter)

    9. Buck-Boost uk converter

    10.Comparison of switch utilizations

    11.Effects of parasitics

    12.References

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    DC, RMS

    DC value (average) of a signal (voltage, current):

    T1 T1

    - -

    DCT 0

    DCT 0

    ,

    0

    21RMS dtvV

    021

    RMS dtiI

    If a waveform can be divided into n harmonics:

    2)(

    2)2(

    2)1(

    2 ... nRMSRMSRMSDCRMS VVVVV

    2)(

    2)2(

    2)1(

    2 ... nRMSRMSRMSDCRMS IIIII

    Problems

    Determine the DC and RMS values of the following signals:

    a) b) c)

    d) e) f)

    g)

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    Answers

    a) ;2 m

    RMSm

    DC

    II

    II

    b)TTII

    TTII mRMS

    mDC

    00 ;2

    c)T

    TUU

    T

    TUU mRMSmDC

    00 ;

    d)T

    TUU

    T

    TUU mRMS

    mDC

    00

    3;

    2

    e)3

    ;2

    m

    RMS

    m

    DC

    II

    II

    f)3

    ;2

    mRMS

    mDC

    UU

    UU

    g) AIAI RMSDC 18.143;17.8

    Problem

    Calculate the power losses of an IGBT during conduction,

    on CE0iC

    M

    Im

    t

    on

    CE0

    TM

    m

    0

    Solution: IC(DC)=3.8A; IC(RMS)=6A; Pd=5.22W

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    Chopper with RLE load

    Voltage transfer function, for CCM:

    DVV

    The PWM switching period:

    o

    io

    i o

    o

    oDC

    Step-down (buck) converter

    L

    io DVV i o

    Current transfer function (CCM):L

    oDC

    o

    DII io /S

    S

    D

    LC

    o

    +

    i o

    C

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    LC design basics*

    Boundary between CCM and DCM (L-design 1):

    fRDLb

    2)1(

    Maximum current ripple through L (L-design 2):

    fL

    DDVI iL

    )1(

    Voltage output ripple (C-design):

    2min8

    )1(

    LfV

    VDC

    o

    o

    * with ideal components (neglecting the voltage drops on the components)

    Problem

    Design L and C for a buck converter with the following

    specifications: Vi=2025V, Vo=10V, Pn=100W, Pmin=10W,

    f=25kHz.

    , m n

    L-current ripple condition: IL0.5A

    C-voltage ripple condition: Vo10mV

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    Step-up converter (Boost)

    L

    VV 1 i o

    Current transfer function CCM :

    D1 LiDC

    io IDI )1( S

    C

    o

    LC design basics*

    Boundary between CCM and DCM (L-design 1):

    DRDLb

    2

    )1( 2

    Maximum current ripple through L (L-design 2):

    fL

    DVI iL

    Voltage output ripple (C-design)

    RfV

    DVC

    o

    o

    min

    *with ideal components

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    Problem

    Design L and C for a boost converter with the following

    specifications: Vi=1218V, Vo=24V, Pn=120W, Pmin=12W,

    = .

    The converter must operate in CCM, for PPmin

    L-current ripple condition: IL0.5A

    C-voltage ripple condition: Vo50mV

    Buck-Boost converter (inverted voltage)

    L

    i

    VD

    V o

    Current transfer function CCM :D1

    L

    io ID

    I

    1S

    S

    D Io

    Vi Vo RL C

    iLC C

    + o

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    LC design basics*

    Boundary between CCM and DCM (L-design 1):

    RDLb)1( 2

    Maximum current ripple through L (L-design 2):

    DVI iL

    Voltage output ripple (C-design)

    DVC omin

    o

    *with ideal components

    Problem

    Design L and C for a buck-boost converter with the following

    specifications: Vi =1636V, Vo= -24 V, Pn=120W, Pmin=12W,

    f=25kHz.

    The converter must operate in CCM, for PPmin

    L-current ripple condition: IL0.8A

    C-voltage ripple condition: Vo50mV

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    Flyback converter (isolated buck-boost converter)

    Voltage transfer function, for CCM:

    1 VnDD

    V it

    o

    21/NNnt

    L (magnetizing inductance) design:

    RDn )1( 22

    fmb

    2

    C design:

    DV

    RfVomin

    Buck-Boost converter (uk)

    Voltage transfer function (CCM): iC1

    io VD

    DV

    1

    IL1

    S-on S-off 0

    Current transfer function (CCM):tvC1

    - L2

    io ID

    I 0 t

    iS

    L1 iL1 IoC1iC1

    +

    L2 iL2

    t0

    L1 L2

    Vi S Vo RCD

    S D

    0

    Vi

    t

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    LC design basics*

    Boundary between CCM and DCM (L1, L2-design 1):

    RDLb)1(

    1 RDLb )1(2

    Maximum current ripple through L (L1, L2-design 2):

    1

    DVI iL 2

    DVI iL

    Voltage output ripple (C-design)

    1 2

    2min

    )1( VDC o

    DVC imin1

    2o

    *with ideal components

    C1

    Problem

    Design L and C for a uk converter with the following

    specifications: Vi =1636V, Vo= - 24V, Pn=120W, Pmin=12W,

    f=25kHz.

    , m n

    L-current ripple condition: IL1,20.8A

    C-voltage ripple condition: Vo10mV, VC12V

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    Comparison of switch utilizations

    Assumptions:

    -The converters operate in CCM;

    - e components are ea an the converter losses are neglected;

    -The current ripple in the inductor is negligible, iL(t)=IL;

    =- o o

    1Buck

    PSUR o

    SUR 0.8 (1-D) (D)

    switch

    utilization

    0.4

    .Buck-Boost

    (D(1-D))ratio

    0

    0.2pkpk

    . . . .D

    Effects of parasitics

    The output capacitor includes a series resistance, rC, known as

    equivalent series resistance (ESR) and is due to the dielectric

    losses and physical resistances of leads and connections;

    The high-frequency current ripple that flows through capacitor

    produces additional voltage drop on ESR;

    o u ons o re uce vo age r pp e on :

    reducing the current ripple => higher L;

    - ,

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    L-design aspects

    L acts as energy storage element in switched-mode converters and

    as filter to smooth out the current harmonics;

    same values of ripple current and filtering requirement;

    The magnetic core losses depends with the square of frequency;

    The coil stray capacitance will cancel the inductor effect above a

    certain frequency (i.e. the coil starts to behave as a capacitor);

    Therefore L-desi n is a tradeoff between switchin fre uenc and

    inductor size.

    References

    1. N. Mohan, T.M. Undeland, W.P. Robbins, Power Electronics

    Converters A lication and Desi n John Wile & Sons 2003

    2. M. H. Rashid, Power Electronics. Circuits, Devices and Applications

    3rd edition, Pearson Education, 2004, USA.

    3. M.H. Rashid, Power Electronics Handbook 3rd edition, Butterworth-Heinemann, 2010, USA.

    4. R. W. Erickson, Fundamentals of Power Electronics, Springer, 2001.

    5. S. M. Sharkh, M.A. Abu-Sara, Power Electronics converters for

    Microgrids, Wiley, 2010, USA.

    6. M.C. Brown, Practical Switching Power Supply Design, Academic

    ress, , .

    7. H. More, Matlab for Engineers, Prentice Hall, 2008.. . ,

    (Romanian version), Transilvania University Press, 2008.