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Chapter 4
Key Technology of WCDMAThis chapter introduces the principles of every
part in a WCDMA transceiver, including the
principle and structure of RAKE receiver, radio
frequency (RF) and intermediate frequency (IF)
processing technology, channel codec technology
and multi-user detection technology.
Source source coder channel coder Modulator
Channel
DemodulatorDestination source encoder channel encoder
M Y
RM
Figure 1.1 Block Diagram of Digital Communication System
Figure 1.1 shows a digital communication system
in a common sense, where a WCDMA transceiver
is installed. Channel codec is Convolutional code
or Turbo code. Modem adopts the technology of
CDMA direct spread spectrum communication.
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Channel coding varies with application data, that
is, AMR adaptive multi-rate code for voice, andITU Rec. H.324 series protocols for image and
multimedia services.
4.1 RAKE Receiver
In CDMA spread spectrum system, channel
bandwidth is far larger than channel flattened
fading bandwidth. This is different from traditional
modulating technology which requires balancing
algorithm to eliminate the inter-symbol
interference. CDMA spread spectrum codes
should be highly auto-correlative. In that case,
delay spread in radio channels can be taken as
signal retransfer. If the delay between multi-path
signals exceeds the length of one chip, the CDMA
receiver will take them as non-correlative noise
without balancing again.
Due to the fact that available information was
included in multi-path signals,, CDMA receiver can
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combine multi-path signals to improve signal
noise ratio (S/N) of receive signals. The functionof RAKE receiver is to receive signals in multiple
paths through several related detectors and
combine them together.. As shown in Figure 1.1, it
is a RAKE receiver, which is a typical diversity
receiver specially designed for CDMA system. The
theory behind is that multi-path signals can be
taken as irrelevant ones when the transporting
delay exceeds one chip period.
Q
I
Combination
and addition
I
Delay estimation
Phase
rotation
Channel
estimation
Delay
balance
I
Q
Path 1
Path 2
Path 3
Baseband
input signal
Time value (path location)
Correlator
with DLL
Local
spread
code
Q
I
Combination
and addition
I
Delay estimation
Phase
rotation
Channel
estimation
Delay
balance
I
Q
Path 1
Path 2
Path 3
Baseband
input signal
Time value (path location)
Correlator
with DLL
Local
spread
code
Figure 1.1 Block Diagram of RAKE Receiver
A correlator with DLL is a demodulating correlator
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with phase-locked loop of early-late gate. The
early-late gate and demodulating correlator differfrom each other by 1/2 (or 1/4) chip respectively.
Subtracting the related output of early-late gate
can be used for adjusting code phase. The
performance of delay loop depends on loop
bandwidth.
Owning to fast fading and noise in the channel,
there are great differences between the actual
received phases of various paths and the phases
of original transmitted signals. Therefore, the
phases should be rotated before combination
based on the results of channel estimation.
Channel estimation in the actual CDMA system is
performed based on pilot symbols in the
transmission signals. Depending on sequentialpilot signals in the transmission signals, there are
two ways of phase prediction, one is based on
sequential pilot and the other is based on decision
feedback technology, as shown in Figure 1.2 and
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Figure 1.3.
Correlator
(Pilot channel)
Baseband I/Q signal
LPF
Predicted phase and
amplitude results
I/Q signal
Correlator
(Pilot channel)
Baseband I/Q signal
LPF
Predicted phase and
amplitude results
I/Q signal
Figure 1.2 Channel Estimation Based on Sequential Pilot Signals
Correlator
Baseband I/Q signal
Predicted phase and
amplitude results
I/Q signal
DMUX
Data symbol
Pilot symbol
LPF
interpolation
Symbol
judgingLPFCorrelator
Baseband I/Q signal
Predicted phase and
amplitude results
I/Q signal
DMUX
Data symbol
Pilot symbol
LPF
interpolation
Symbol
judgingLPF
Figure 1.3 Channel Estimation Based on Interrupted Pilot
Condition Using Decision Feedback Technology
LPF is a low pass filter, filtering the noise in
channel estimation output, whose bandwidth is
generally higher than the channel fading rate.
When using interrupted pilot, we should adopt
interpolation technology to perform channel
estimation in the interval of pilot. When using
decision feedback technology, we should first
decide the data symbols in the channel, and then
take the decided results as apriori information
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(similar to pilot) to perform complete channel
estimation, and accordingly obtain good channelestimation results through low pass filtering. The
shortcoming of this way is low accuracy of
channel estimation and big decoding delay in
case of serious noise, due to non-linear and non-
causal prediction technology.
The function of delay estimation is to obtain signal
energy distribution in different time delay locations
through matched filter (as shown in Figure 1.4),
recognize multi-path locations with high energy
and distribute their time value to different receive
paths of RAKE receiver. The measuring precision
of the matched filter can be up to 1/4 ~ 1/2 chip,
but the interval in different receive paths of RAKE
receiver is one chip. In the actual implementation,if the speed of updating delay estimation is very
fast (such as once scores of ms), the phase-
locked loop of early-late gate is not necessary.
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Local spreading codes and scrambling codes
N N-1 0
N N-1 0
Serial input
sampling data
Local spreading codes and scrambling codes
N N-1 0
N N-1 0
Serial input
sampling data
Figure 1.4 Basic Structure of Matched Filter
The major part used for delay estimation is
matched filter, whose function is to correlate the
input data and local codes of different phases and
accordingly obtain correlation energy of different
codes and phases. If the sampling data input in
serial are the same as the phases of local spread
spectrum code and scrambled code, the
correlation energy is the greatest, with a
maximum in the output end of the filter.
Depending on correlation energy, the delay
estimator can obtain multi-path arrival time value.
From the perspective of implementation, there are
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chip level processing and symbol level processing
for the RAKE receiver. For chip level processing,correlator, local code generator and matched filter
are included, while for symbol level processing,
channel estimation, phase rotating and
combination are included. Generally, chip level
processing can be implemented with ASIC
component, while symbol level processing can be
implemented with DSP. Although the
implementation and functions of RAKE receiver of
a mobile station are different from those of a base
station, the principles are just the same.
For several receiver antennas with diversity
reception, we can process multiple paths received
by several receiver antennas in the above way.
RAKE receiver can receive not only multiple pathsof the same antenna but also multiple paths of
different antennas. In terms of RAKE receiving,
the two diversities do not vary essentially.
However, the processing of base-band would get
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more complex as the data of multiple antennas
requires dividing control processing.
4.2 CDMA RF and IF Designing Principles
4.2.1 CDMA RF and IF Architecture
Duplexer
Rx filter
IF demix filter ADCDigital lower
converterBasebandprocessor
Lower converter
Data
I/O
I
Q
IF smooth filter DACDigital upper
converter
I
Q
Upper converter
Tx filter
Local
oscillator
Power amplifier
RF AGC
RF AGC
Local
oscillator
Duplexer
Rx filter
IF demix filter ADCDigital lower
converterBasebandprocessor
Lower converter
Data
I/O
I
Q
IF smooth filter DACDigital upper
converter
I
Q
Upper converter
Tx filter
Local
oscillator
Power amplifier
RF AGC
RF AGC
Local
oscillator
Figure 1.1 Block Diagram of CDMA RF and IF Principles
Figure 1.1 is a block diagram of CDMA RF and IF
principles. For the RF part, it is a traditional
analog structure where valid signals are translated
into IF signals. The downlink channel of RF part
mainly consists of automatic gain control (RF
AGC), receive filter (Rx filter) and down-converter.
The uplink channel of the RF part mainly consists
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of automatic gain control (RF AGC), secondary
up-converter, wideband linear power amplifier andRF transmit filter. The IF part consists of the de-
aliasing filter, the down-converter and the ADC for
downlink processing, and the IF, a smoothing
filter, the up-converter and the DAC for uplink
processing. Regarding WCDMA digital down-
converter, its bandwidth of output base-band
signal is larger than that of the IF signal by 10%,
therefore, called wideband signal, it is different
from the general GSM signal and the first
generation signal.
4.2.2 CDMA RF Designing Performance and
Considerations
As mentioned above, CDMA signal is wideband
signal. Therefore, the RF part must be designed to
be suitable for wideband low-power spectrum
density signal. CDMAs large dynamic range, high
peak factor (due to linear modulating and multi-
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code transmission), and precise high-speed
power control loop are great challenges to thelinearity and efficiency of power amplifier.
CDMA makes very high requirements for the
linearity and efficiency of the RF front end.
Linearity is demanded for strict output spectrum
mask and, at the same time, the great fluctuation
of output signal envelope. To ensure the power
amplifier is efficient enough, we should keep its
operating level around 1 dB point.
To make the mobile station more compact andpower-efficient, one-step direct conversion should
be implemented from baseband to RF or from RF
to baseband at both the transmit end and the
receive end. Such technology is difficult in that the
frequency mixer must be completely linear to
avoid any possible intermodulation product
between two adjacent channels. In addition, input
isolation of the frequency mixer must be good
enough to avoid DC due to self-mixing.
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The performances of AGC and LNA in RF part are
crucial as well. In WCDMA designing, the noiseindex of AGC should be around 80dB, while that
of LNA should be lower than 4dB, because it
decides the overall noise index of the receiver.
Analog RF components cause great RF index
changes and individual diversity. We should
emulate the total receiver performance loss
caused by each RF component in the worst case,
so that a group of stable RF designing parameters
can be obtained. Moreover, according to the latest
designing scheme, the number of analog
components should be made as small as
possible, which makes it necessary to move ADC
and DAC closer to RF part. However, when
considering the present signal processingcapability of the component, the digital IF
technology is a commonly used for designing.
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4.2.3 Digital IF Technology
The sampling law shows that, if we perform equal-
interval sampling at interval of 1/2fHsecond for the
continuous time signal m(t), with a frequency band
limited at (0,fH) Hz, m(t) can be definitely
determined according to the sampling result.
In this case, 2fHis called Nyquist frequency.
Typically, a modern receiver is structured such
that analog-digit conversion and sampling are
performed by the IF component. The specific
process is: IF signal M() with the bandwidth of B
undergoes IF sampling with fs 2B(1 +/n), to get
the resulting signal MS(), which further becomes
the quantized and sampled low IF signal M'S()
after passing the low pass filter H(). The final
signal has the same frequency spectrum as that
of the original one.
It can be seen from the above process that IF
sampling can be done with a frequency lower than
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the highest valve of signal frequency as long as
the frequency meet the specified conditions. In themeantime, frequency conversion can be achieved
through IF sampling, that is, converting the signal
to a lower IF, and multiplying the common
frequencies in the numeric field, and the base-
band diversities I and Q can be deduced.
4.3 Diversity Reception Principle
Radio channel is a random time-specific channel,
whose fading feature will reduce the performance
of the communication system. There are several
measures to avoid fading, such as channel
coding/decoding technology, anti-fading receive
technology or spread spectrum technology.
Diversity reception technology is considered as an
effective and economical anti-fading technology.
As we all know, the signal received in radio
channel is an combination of multi-path
components arriving at the receiver. If the signals
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of different paths obtained at the receive end at
the same time can be combined into the wholereceive signal properly, the effect of fading will be
reduced. That is how diversity is designed.
Literally, the meaning of diversity is to obtain
compound signals separately and then combine
them. The signals, if statistically independent, can
be combined such that the performance of the
system can be improved greatly.
Those received signals, completely or almost
independent of each other, can be obtained by the
following receiving means: different paths,
different frequencies, different angles and different
polarizations.
1) Space Diversity: set several antennas upon the
receive end or the transmit end, and leave
enough space (generally exceeding 10 signal
wavelength) between each two antennas to
ensure the signals sent/received in each
antenna are mutually independent. Figure 1.1
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is an example of dual-antenna transmit
diversity to improve receive signals. Thanks todual-antenna transmit diversity, the
independent receive paths obtained by the
receiver are increased and accordingly
combination effect is gained:
Path 1
Antenna 1
Path 2
Transmitting
diversity
processing
Data flow
Data flow 1
Data flow 2
Restored data flow
Antenna 2
Path 1
Antenna 1
Path 2
Transmitting
diversity
processing
Data flow
Data flow 1
Data flow 2
Restored data flow
Antenna 2
Figure 1.1 Orthogonal Transmit Diversity Principle
The principle of orthogonal transmit diversity is
shown in Figure 1.1. The two antennas transmit
different data: antenna 1 transmits the data in
even location while antenna 2 transmits the data
in odd location. Owing to the irrelevant transmit
data, the data arriving at receiver antenna via
different antenna paths have corresponding
diversity, and accordingly the power of data
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transmission can be reduced. In the meantime,
the reliability of data transmission is greatlyimproved due to lower bit rate of single antenna
transmit data. Therefore, transmit diversity can
increase the data transmission speed of the
system.
2) Polarization Diversity: receive horizontal
polarized wave and perpendicular polarized
wave respectively.
Time Diversity: Another way of diversity is to
combine irrelevant signals transmitted
asynchronously. Frequency Diversity: The same
information is transmitted with several different
carrier frequencies. If frequency difference interval
of each carrier frequency is so large that it
exceeds channel relevant bandwidth, the signalstransmitted with carrier frequencies are irrelevant
of each other. Angle Diversity: Signals are not
related because antennal beams point to different
direction. For example, set several irradiators on
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the microwave antenna to generate little-related
beams. The diversities can be combined inpractice because they are not mutually repulsive.
We can adopt different ways to combine diversity
signals:
1) Selective Combination (SC): Select the signal
with the best S/N from several discrete ones as
the receive signal.
2) Equal Gain Combination (EGC): Combine
several discrete signals by the same branch
gain and take the combined signal as the
receive signal.
3) Maximum Ratio Combination (MRC): Control
each combined branch gain to make them in
proportion to the S/N of the existing branch,
and then combine them to get receive signal.
The above ways are different between the
diversity gains in improving the combined S/N.
Generally, diversity reception is effective to
improve the effect of radio channel reception.
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0
2
4
6
8
10
12
1 2 3 4 5 6 7 8 9 10
Max ratio combination
Equal-gain combination
Optimal choice
Improvement(r)
(dB)
Diversity number k
0
2
4
6
8
10
12
1 2 3 4 5 6 7 8 9 10
Max ratio combination
Equal-gain combination
Optimal choice
Improvement(r)
(dB)
Diversity number k
Figure 3.1 Comparison of different combinations
Figure 3.1 shows the improvement of receiving
effects of different combinations. As the diversity
number K increases, the improvement of SC is
not ideal, while that of EGC and MRC is better,
whose difference is only about 1 dB.
4.4 Channel Coding
Channel coding is adding some extra codes to a
digital sequence M by definite rules so that
irregular information sequence M becomes a
regular digital sequence Y (code sequence). That
is to say, in code sequence, every code of
information sequence is related to extra code. At
the receiving end, the channel encoder encodes
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with this prescient coding rules, or verifies that the
received digital sequence R conforms to the setrule to find out errors in R and then corrects them.
That is the basic idea of channel coding, namely,
verifying and correcting the errors during
transmission based on correlativity.
Generally, digital sequence M is transmitted with K
codes as a group. We call the one with K-code
block an information code block. Channel encoder
adds some extra codes to each information code
block by definite rules, and so the code block with
n-code is constituted. Such n codes are mutually
related, that is, the extra n-k codes are called the
supervising codes of this code block. In terms of
information transmission, supervising codes are
redundant, as it carries no information. However,such redundancy gives the codes some error
detection and correction capability, so the
reliability of transmission is increased and error
rate is reduced. On the other hand, if we require
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the speed of information transmission to remain
constant, after supervising codes are added, theduration of each code in the code block should be
reduced. For a binary code, pulse width should be
also reduced. If the normalized width of each code
pulse is 1 before coding, it should be k/n after
coding, so channel bandwidth should be spread
by n/k times. In this case, bandwidth redundancy
substitutes for reliability of channel transmission. If
the speed of information transmission is allowed
to be slower, the duration of each code after
coding can remain the same. In this case,
bandwidth redundancy substitutes for reliability of
channel transmission.
As shown in Table 1.1, there are great gaps
between coding gains from different codingmethods and the ideal coding gain (up to
Shannon limit).
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Table 1.1 BPSK or QPSK Coding Gain
Coding Adopted Coding
Gain
(dB@BER
= 10-3)
Coding
Gain
(dB@BER
= 10-5)
Data
Speed
Ideal Coding 11.2 13.6
Cascaded Code (RS
and Convolution Code
Viterbi Coding)
6.5 ~ 7.5 8.5 ~ 9.5 moderate
Convolution Code
Sequence Coding (SoftDecision)
6.0 ~ 7.0 8.0 ~ 9.0 moderate
Cascaded Code (RS
and Group Code)
4.5 ~ 5.5 6.5 ~ 7.5 Very High
Convolution Code
Viterbi Coding
4.0 ~ 5.5 5.0 ~ 6.5 High
Convolution Code
Sequence Coding
(Hard Decision)
4.0 ~ 5.0 6.0 ~ 7.0 High
Group Code (Hard 3.0 ~ 4.0 4.5 ~ 5.5 High
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Decision)
Convolution Code
Threshold Coding
1.5 ~ 3.0 2.5 ~ 4.0 Very High
It is observed that, for the same modulating,
coding gains vary with different coding schemes.
The coding schemes we usually adopt are
convolution code, Reed-Solomon code, BCH code
and Turbo code, etc. Convolution code is used for
voice and low-speed signaling in WCDMA, while
Turbo code is used for data encoding.
4.4.1 Convolution Code
The n codes generated by the convolution coder
during any definite time is dependent on K
information bits during this period and the number
of information bits during the former N-1 period oftime. At this moment, supervising code monitors
the information during the N period of time when
the number of codes nN is called constraint
length.
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The decoding schemes of convolution code are as
follows: threshold decoding, hard decision Viterbidecoding and soft decision Viterbi decoding.
Among these decoding schemes, the best one is
soft decision Viterbi decoding, which is usually
adopted. Compared with hard decision Viterbi
decoding, it is not much more complex, but its
performance is better by 1.5 ~ 2 dB.
4.4.2 Turbo Code
We are striving to approach Shannon limit in
coding field, where Turbo code is an innovation
milestone. Grid code is close to Shannon limit in
case of bandwidth-limited channels, while Turbo
code is especially applicable to bandwidth-
unlimited channels, such as deep space
communication and satellite communication.
Theory emulation shows that, in the AWGN
channel with 0.7dB Eb/N0, Turbo code with 1/2
code rate has bit error rate of 10-5.
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Two or more basic coders are cascaded in parallel
via one or more interweavers, and so Turbo codeis constituted as shown in Figure 1.1. Turbo code
is based on the correction of the algorithm and
structure of the traditional cascade code. The
positive feedback of iterative decoding is
cancelled thanks to the introduction of internal-
interweaver. The algorithm of Turbo iterative
decoding involves SOVA (soft output Viterbi
algorithm) and MAP (maximum posterior
probability algorithm) and so on. Thanks to each
iterative performance of MAP algorithm excels
Viterbi algorithm, iterative decoding of MAP
algorithm can get more coding gains.
Interleafer
Convolution encoder 1
Holingmultiplexing
Input m ty t
Convolution encoder 2
Output
Interleafer
Convolution encoder 1
Holingmultiplexing
Input m ty t
Convolution encoder 2
Output
Figure 1.1 Turbo Coder
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4.5 Multi-User Detection Technology
Multi-user detection (MUD) technology can
improve the system performance and increase the
system capacity by canceling the inter-cell
interference. In addition, MUD technology can
effectively release the near/far effect in direct
sequence spread spectrum CDMA system.
As the channels are non-orthogonal and different
users spread spectrum codes are non-orthogonal,
there is mutual interference between users. MUD
is to cancel the mutual interference between multi
users. Generally speaking, for uplink MUD, only
the inter-cell interference can be canceled, while
the intra-cell interference is difficult to cancel due
to lack of necessary information (such as the
detailed information of users in adjacent cells).
For downlink MUD, only the interference in
common channel (such as pilot frequency and
broadcast channel) can be canceled.
The system model of MUD can be shown in
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Figure 1.1: each user transmits data bit 1b , 2b ,, Nb
, frequency is spread by spread spectrum codeword via non-orthogonal fading channel in the
space, and noise n(t) is added, then the user
signals received at the receive end is correlated to
synchronous spread spectrum code word and the
correlation is composed of multiplier and integral
cleaner. The interference between users is
removed with MUD algorithm from the de-spread
result, thus obtaining the estimated value of users
signal 1b , 2b ,, Nb .
It is observed from the following figure that the
performance of MUD depends on synchronized
spread spectrum code word tracing of the
correlator, detection performance of each user
signal, relative energy and the accuracy ofchannel estimation.
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Spreading
code word 1
Noise n (t) Multi-userdetectionalgorithm
Integral
cleaner
Spreading
code word 2
Spreading
code word k
Integralcleaner
Integral
cleaner
Spreading
code word 1
Noise n (t) Multi-userdetectionalgorithm
Integral
cleaner
Spreading
code word 2
Spreading
code word k
Spreading code word 1
Spreading code word k
Integralcleaner
Integral
cleaner
Spreading code word 2
1b
1b 1b
1b
1b
1b
1b
1b
1b
1b1b
1b
2b
kb
1b
1b1b
1b
2b
1b
kb
Figure 1.1 System Model of MUD Technology
According to the uplink MUD, only the intra-cell
interference can be canceled. Provided that the
inter-cell interference energy was f times of the
intra-cell interference energy, the capacity in thecell would increase by (1+f)/f without intra-cell
interference. According to the rule that the
transmit power attenuates linearly by 4 powers of
distance, the inter-cell interference is 55% of intra-
cell interference. Therefore, MUD would ideally
reduce 2.8 times of interference. However in
practice, the validity of MUD is below 100%. The
validity of MUD depends on the detection
methods, traditional receiver estimation accuracy
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and intra-cell user service model. For example, if
there are some high-speed data users in the cell,MUD is adopted to cancel the interference power
caused by these high-speed data users, which
obviously can be more effective to increase
system capacity.
But the shortcoming of it is that noise would be
increased and demodulation signal would be
greatly delayed. Decorrelator is shown in Figure
1.2.
Interference cancellation is to estimateinterference from different users and multiple
paths and then cancel the interference from the
receive signals. Serial interference cancellation
(SIC) is to gradually cancel the interference
caused by the biggest user, while parallel
interference cancellation (PIC) is to
simultaneously cancel the interference cause by
other users.
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R-1
Multipath
delay
estimation
Correlation
calculation
Soft judgingChannel
decoderH 1(t)
H 2(t)
Match filterS1
S2
H K (t)SK
[ ]1 r
r 1R =
Match filter
Match filter
Soft judging
Soft judging
Channel
decoder
Channel
decoder
R-1
Multipath
delay
estimation
Correlation
calculation
Soft judgingChannel
decoderH 1(t)
H 2(t)
Match filterS1
S2
H K (t)SK
[ ]1 r
r 1R =
Match filter
Match filter
Soft judging
Soft judging
Channel
decoder
Channel
decoder
Figure 1.2 Decorrelator
PIC is, for each user, to cancel signal energy
caused by other users at every level of
interference cancellation and demodulate it. The
interference caused by other users can be
basically canceled after 3 ~ 5 times of such
interference cancellation. Note that at every level
of interference cancellation, not all signal energy
caused by other users can be canceled. We just
multiply it by a relatively small coefficient to avoid
the growing error in the traditional receive
detection. The advantage of PIC is that it can
easily implement multi-user interference
cancellation and the delay of it is better than that
of SIC.
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As far as WCDMA uplink MUD is concerned, the
present ideal technology is PIC, because itdemands just 3 to 5 times of resources traditional
receiver demands, and the data path delay is also
small.
As far as WCDMA downlink MUD is concerned, it
focuses on canceling the interference of downlink
common pilot channel, shared channel and
broadcast channel and the interference of
common channels in a co-frequency adjacent
base station.
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