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I hereby declared that I have read this thesis and in my opinion this thesis is sufficientin terms of scope and quality for the award of the degree of Master of Engineering
(Electrical-Electronics & Telecommunication)
Signature : __________________________
Name : Prof. Dr. Tharek bin Abd Rahman
Date : 4th
April 2005
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i
PERFORMANCE STUDY ON HIGH DATA RATES
MODULATION TECHNIQUES OF W-CDMA IN MULTIPATHFADING CHANNEL
MUHAMMAD NAJIB BIN ISMAIL
A project report submitted in partial fulfillment of the
requirements for the degree of
Master of Engineering (Electrical-Electronics & Telecommunication)
Faculty of Electrical Engineering
University Technology Malaysia
APRIL 2005
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ii
I declare that this project report entitled Performance Study on High Data Rate
Modulation Techniques of WCDMA in Multipath Fading Channel is the result of my
own research except as cited in the references. The project report has not been accepted
for any degree and is not concurrently submitted in candidature of any other degree.
Signature : __________________________
Name : MUHAMMAD NAJIB BIN ISMAIL
Date : 4th
April 2005
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DEDICATION
To my dearest wife, son and parents
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iv
ACKNOWLEDGEMENT
I would like to express my gratitude and appreciation to my project supervisor
Professor Dr. Tharek Abdul Rahman for all his guidance, helps and patience during the
course of this project.
Moreover, I extend my gratitude to my friends Azlin Mohd Fahmi and Maslinda
Rasli for their opinions, advices and thorough discussions for making this project well
organized, efficient and successful.
Last but not least, I would like to say thank you to my family especially to my wife
for her patience and advices throughout my course of work on this project.
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v
ABSTRACT
Downlink transmission (base station to mobile terminal) using high data rate M-
ary Quadrature Amplitude Modulation (QAM) and Quadrature Phase Shift Keying
(QPSK) modulation schemes are considered in a Wideband-Code Division Multiple
Access (W-CDMA) system. The performances of these modulation techniques are
evaluated when the system is subjected to a number of users as well as noise and
interference in the channel. Additive White Noise Gaussian (AWGN) and multipath
Rayleigh fading are considered in the channel. Computer simulation tool, MATLAB,
will be used throughout the research to evaluate Bit-Error-Rate (BER) for W-CDMA
system models. Two approaches are used in this simulation. They are simulations using
Simulink and simulations using M files. A study of different modulation techniques is
needed so that a W-CDMA system can choose suitable modulation technique to suit the
channel quality, thus delivering optimum and efficient data rate to mobile terminal. It is
discovered that the performance of 16-QAM is significantly degraded in AWGN and
multipath Rayleigh fading channel compared to that of QPSK. Error correction coding is
needed to be used in this system particularly with 16-QAM to ensure better performance
of WCDMA system.
Index Terms Multipath Rayleigh fading, AWGN, Direct Sequence Spread Spectrum
(DSSS), Code Division Multiple Access (CDMA), BER, signal-to-noise ratio (SNR),
QPSK and 16-QAM
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vi
ABSTRAK
Projek ini melibatkan kajian mengenai transmisi jalinan ke bawah (downlink)
(stesen tapak ke terminal boleh gerak) yang melibatkan penggunaan teknik-teknik
modulasi QPSK dan 16-QAM di dalam Pemodulatan Pembahagian Kod Pelbagai
Capaian Lebar Jalur Luas (Wideband Code Division Multiple Access, WCDMA).
Prestasi teknik-teknik modulasi ini dinilaikan ke atas sistem WCDMA yang dikenakan
hingar dan interferen pada saluran (channel) sistem ini. Pertambahan Bunyi Hingar Putih
Gaussian (AWGN) dan kelenturan pelbagai laluan Rayleigh (multipath Rayleigh fading)
dipilih untuk digunakan pada saluran di dalam sistem ini. Di dalam kajian ini, programcomputer MATLAB telah digunakan untuk mensimulasikan sistem WCDMA untuk
menilai kadar kesilapan bit di dalam sistem WCDMA. Dua kaedah telah digunakan iaitu
simulasi menggunakan Simulink dan simulasi menggunakan file M. Penyelidikan
terhadap teknik-teknik modulasi adalah diperlukan bagi sistem WCDMA supaya teknik
modulasi yang sesuai dapat digunakan secara dinamik oleh sistem ini supaya ia dapat
disesuaikan dengan keaadaan saluran. Kaedah ini adalah untuk memastikan
penghantaran data daripada stesen tapak ke terminal boleh gerak adalah pada tahap yang
laju, efisyen dan optimum. Keputusan simulasi computer ini telah menunjukkan
penurunan prestasi bagi teknik modulasi 16-QAM di dalam saluran AWGN dan
kelenturan pelbagai laluan Rayleigh jika ia dibandingkan dengan QPSK. Kod
pembetulan kesilapan adalah diperlukan di dalam sistem ini terutamanya jika 16-QAM
digunakan untuk memastikan sistem WCDMA berada pada keadaan yang baik.
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vii
TABLE OF CONTENT
ACKNOWLEDGEMENT iv
ABSTRACT v
ABSTRAK vi
TABLE OF CONTENT vii
LIST OF TABLES xi
LIST OF ABBREVIATION xv
LIST OF APPENDIX xvi
1 INTRODUCTION 1
1.1 Background of the Problem 1
1.2 Problem Statements 2
1.3 Project Objective 2
1.4 Scope of Work 4
1.5 Significant of the Project Research 5
2 MODULATION SCHEMES IN WCDMA 7
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2.1 Bit Rate and Symbol Rate 9
2.2 Quadrature Phase Shift Keying (QPSK) 10
2.3 M-ary Quadrature Amplitude Modulation (QAM) 11
2.4 Wideband-Code Division Multiple Access (W-CDMA) 12
2.4.1 Direct Sequence Spread Spectrum (DSSS) 12
2.4.2 Code Division Multiple Access (CDMA) 15
2.5 Noise and Interference 15
2.5.1 Additive White Noise Gaussian (AWGN) 16
2.5.2 Rayleigh Fading 17
2.6 Bit Error Rate (BER) 19
2.7 Signal-to-Noise Ratio (SNR) 20
2.8 DSSS-CDMA Bit-Error Probability Calculations 20
2.9 Theoretical DSSS-CDMA System and Channel Models 21
2.9.1 Transmitter Model 21
2.9.2 Receiver Model 232.9.3 Channel Model 23
2.9.3.1 AWGN 23
2.9.3.2 Rayleigh Fading 25
3 CONFIGURATIONS ON WCDMA SYSTEM 28
3.1 Simulation Methodology 29
3.2 Simulation Using Simulink 30
3.2.1 Simulation in Phase 1: WCDMA System in AWGN Channel 31
3.2.1.1 Assumptions in Phase 1 31
3.2.1.2 Transmitter Design 35
3.2.1.2.1 User Data Sequence Generator 35
3.2.1.2.2 Spreading Sequence Generator 36
3.2.1.2.3 Spreader 38
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ix
3.2.1.3 Modulation Techniques 39
3.2.1.3.1 QPSK Modulator 39
3.2.1.3.2 16-QAM Modulator 42
3.2.1.4 Channel Design 43
3.2.1.5 Receiver Design 43
3.2.1.5.1 QPSK Demodulator 43
3.2.1.5.2 16-QAM Demodulator 45
3.2.1.6 Despreader 45
3.2.1.7 Error Rate Calculation 46
3.2.1.8 Display 473.2.1.9 Performance Analysis for Phase 1 48
3.2.2 Simulation Phase 2: WCDMA system in AWGN and Multipath Rayleigh
Fading 50
3.2.2.1 Channel 53
3.2.2.2 Performance Analysis for Phase 2 55
3.3 Simulation Using M file 56
3.3.1 Generation of Spreading Code 56
3.3.2 Code Generation by Linear Feedback Shift Register 58
3.3.3 M-Sequence 59
3.3.4 Configuration of Transmitter and Receiver 61
3.3.5 Steps Taken to Realize the Simulation in dscdma.m file 66
3.3.6 Assumption and Limitation 67
4 PERFORMANCE ANALYSIS ON WCDMA SYSTEM 68
4.1 Simulation Using Simulink 69
4.1.1 Performance Analysis of QPSK modulation technique of WCDMA in
AWGN 69
4.1.2 Performance Analysis of QPSK modulation technique of WCDMA in
AWGN and Multipath Fading Channel 71
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x
4.1.3 Performance Analysis of 16-QAM modulation technique of WCDMA in
AWGN 74
4.1.4 Performance Analysis of 16-QAM modulation technique of WCDMA in
AWGN and Multipath Fading Channel 75
4.2 Simulation Using M files 78
4.2.1 Performance Analysis of QPSK modulation technique of WCDMA in
AWGN 78
4.2.2 Performance Analysis of QPSK modulation technique of WCDMA in
AWGN and Multipath Fading Channel 79
4.2.3 Performance Analysis Comparison of QPSK modulation technique of
WCDMA Between AWGN and Rayleigh Fading Channel 83
4.2.4 Performance Analysis of 16-QAM modulation technique of WCDMA in
AWGN 89
4.2.5 Performance Analysis of 16-QAM modulation technique of WCDMA in
AWGN and Multipath Fading Channel 90
4.3 Analysis and Discussion 90
5 CONCLUSION 92
5.1 Conclusion 92
5.2 Suggestion for Future Work 93
REFERENCES 95
APPENDIX 98
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xi
LIST OF TABLES
Table no. Title Page no.
3.1 Parameters for Bernoulli Binary Generator Block 35
3.2 Parameters used in PN Sequence Generator Block 36
3.3 Parameters used in QPSK Modulator Passband Block 40
3.4 Parameters used in M-QAM modulation block 42
3.5 Parameters used in AWGN block 43
3.6 Parameters used in QPSK Demodulator Passband Block 44
3.7 Parameters used in 16-QAM Demodulator Passband Block 45
3.8 Parameters used in Error Rate Calculation Block 46
3.9 Parameters used in Display Block 48
3.10 Parameters used in multipath Rayleigh fading channel 53
4.1 Simulation result for evaluation on BER vs. SNR for 2-ray
AWGN channel for 1 user when the number of data is
200,000
78
4.2 Simulation results for evaluation on BER vs. SNR for 2-ray
Multipath Rayleigh Fading channel for 1 user when the
number of data is 200,000 at 60 kmph
80
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xiii
LIST OF FIGURES
FIGURE NO. TITLE PAGE NO.
2.1 Constellation diagram of a QPSK system 12
2.2 Constellation diagram of a 16-QAM system 12
2.3 CDMA 15
2.4 Relationship among channel correlation function and power
density function
18
3.1 Simulation process for W-CDMA system models 30
3.2 WCDMA Model using QPSK modulation technique in
AWGN channel
33
3.3 W-CDMA Model using 16-QAM modulation technique in
AWGN and multipath fading channel
34
3.4 W-CDMA Model with Multipath Raleigh fading channel andAWGN channel using QPSK Modulation Technique
51
3.5 W-CDMA Model using 16-QAM in AWGN and Multipath
Raleigh fading channel
52
3.6 Three-stage M-sequence 61
3.7 WCDMA system configured using m files 62
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xiv
4.1 Performance of WCMA system using QPSK in AWGN
channel
70
4.2 Performance of WCDMA system using QPSK in multipath
fading channel at 60 kmph
71
4.3 Performance of WCDMA system using QPSK in multipath
fading channel for 90 kmph
72
4.4 Performance of WCDMA system using QPSK in multipath
fading channel at 120 kmph
73
4.5 Performance of WCDMA system using 16-QAM in AWGN 74
4.6 Performance of WCDMA system using 16-QAM in
multipath fading channel at 60 kmph
75
4.7 Performance of WCDMA system using 16-QAM in
multipath fading channel at 90 kmph
76
4.8 Performance of WCDMA system using 16-QAM in
multipath fading channel at 120 kmph
77
4.9 Performance of WCDMA in 2-Rays AWGN Channels for 1user
79
4.10 Performance of WCDMA in 2-Rays Multipath Rayleigh
Fading Channels for 1 user
82
4.11 Performance Comparison of WCDMA in 2-Rays Between
AWGN and Multipath Rayleigh Fading Channels for 1 user
85
4.12 Performance Comparison of WCDMA in 2-Rays Between
AWGN and Multipath Rayleigh Fading Channels for 5 user
88
4.13 Performance Comparison of 16-QAM in WCDMA system in
AWGN channel
89
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xv
LIST OF ABBREVIATION
WCDMA Wideband Code Division Multiple Access
UMTS Universal Mobile Telecommunication System
GMSK Gaussian Minimum Shift Keying
GSM Global System for Mobile Communication
AWGN Additive White Noise Gaussian Noise
QPSK Quadrature Phase Shift Keying
QAM Quadrature Amplitude Modulation
BER Bit Error Rate
SNR Signal to Noise Ratio
PN Pesudo-Noise
AMC Adaptive Modulation and Coding
HSDPA High Speed Downlink Packet Access
PDF Probability Density Function
dB Decible
ISI Inter-Symbol Interference
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xvi
LIST OF APPENDIX
APPENDIX
NO.
TITLE PAGE NO.
1.1 Matlab Source Codes for Simulation Using Simulink 98
1.1.1 Generic Source Codes of Simulation for QPSK of WCDMA
system either in AWGN or Multipath Fading channel or both
98
1.1.2 Generic Source Codes of Simulation for 16-QAM of
WCDMA system either in AWGN or Multipath Fading
channel or both
99
1.2.1 Source Codes for Simulation of Sub-System of WCDMA 100
1.2.1.1 Source Codes for Simulation of Autocorrelation Function of
a Sequence
100
1.2.1.2 Source Codes for Simulation of Cross-correlation Function
of a Sequence
100
1.2.1.3 Source Codes for Simulation of Generation Function of M
Sequence
101
1.2.1.4 Source Codes for Simulation of Shifting the Contents of the
Register
102
1.2.1.5 Source Codes for Simulation of Data Spread Function 104
1.2.1.6 Source Codes for Simulation of Data Despread Function 105
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xvii
1.2.1.7 Source Codes for Simulation of a Function to Sample the
Time
106
1.2.1.8 Source Codes for Simulation of a Function to Add Gaussian
Noise
107
1.2.2 Source Codes for Simulation of Main-System of WCDMA 108
1.2.2.1 Source Codes for Simulation of the Main Program of DS-
WCDMA System
108
1.2.3 Source Codes for Simulation of BER vs EbNo of WCDMA
System
113
1.2.3.1 Source Codes for Simulation of QPSK of WCDMA Systemin AWGN Channel
113
1.2.3.2 Source Codes for Simulation of QPSK of WCDMA System
in Multipath Rayleigh Fading Channel with Doppler Shift
(60kmph, 90kmph & 120kmph)
113
1.2.3.3 Source Codes for Simulation of QPSK of WCDMA System
for AWGN vs Multipath Rayleigh Fading Channel
115
1.2.3.4 Source Codes for Simulation of QPSK of WCDMA System
for AWGN vs Multipath Rayleigh Fading Channel for a
Single User
117
1.2.3.5 Source Codes for Simulation of QPSK of WCDMA System
for AWGN vs Multipath Rayleigh Fading Channel for a Five
(5) Users
118
1.2.3.6 Source Codes for Simulation of 16-QAM of WCDMA
System in AWGN Channel
119
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CHAPTER 1
INTRODUCTION
1.1 Background of the Problem
W-CDMA system has been identified by Universal Mobile Telecommunication
System (UMTS) as the platform of the 3
rd
generation cellular communication system.Unlike conventional narrowband signal of 2
ndgeneration (2G) communication system,
W-CDMA uses noise-like broadband frequency spectrum where it has high resistance to
multipath fading. High data rate signal transmission can be transmitted over the air by
using W-CDMA system, thus enabling large data transmission of multimedia rich
applications such as high-resolution pictures and video to end-users. Thus, suitable
modulation technique and error correction scheme have to be used in W-CDMA system.
In 2G network, modulation scheme such as GMSK is widely used in Global System of
Mobile Communication (GSM). GMSK can only deliver data rate of 1 bit per symbol.
Obviously, such modulation scheme is not suitable for the next communication system.
Thus, there is a need to study the performance of new modulation technique that could
deliver higher data rate effectively in a multipath fading channel.
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1.2 Problem Statements
To deliver multimedia content application over cellular networks, a high data rate
modulation scheme is one of the important criteria besides good error correction coding.
However, the implementation of high data rate modulation techniques that have good
bandwidth efficiency in W-CDMA cellular communication requires perfect modulators,
demodulators, filter and transmission path that are difficult to achieve in practical radio
environment. Modulation scheme that capable to deliver more bits per symbol is
susceptible to errors caused by noise and interference in the channel. Moreover, errors
can be easily produced as the number of users is increased and the mobile terminal is
subjected to mobility.
1.3 Project Objective
The objectives and aims of this project are to look at the performance of high
data rate modulation techniques at channels that are subjected to Additive White
Gaussian Noise (AWGN) and multipath Rayleigh fading. Modulation schemes that will
be considered in this project are Quadrature Phase Shift Keying (QPSK) and 16-ary
Quadrature Amplitude Modulation (16-QAM). This performance study will be carried
out by varying the chip rate of pseudo-noise (PN) generator. Furthermore, multiple
access scheme i.e. WCDMA will be also studied by comparing certain number of users
under static and mobility environment that are subjected to AWGN and multipath
Rayleigh fading. The performances of WCDMA under these channels fading are based
on Bit Error Rate (BER) at downlink (base station to mobile terminal) transmission.
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There will be three WCDMA wireless cellular system models that will be used in
this project. The models are
1. WCDMA system in AWGN channel
2. WCDMA system in AWGN and Multipath Rayleigh Fading.
3. Multi-user WCDMA system in AWGN and Multipath Rayleigh Fading.
Relationship for multiple rays using QPSK and QAM in W-CDMA system models
for the followings parameters will be obtained using MATLAB. They are:
1. Bit Error Rate (BER) versus Signal-to-Noise ratio (SNR) in AWGN channel for
QPSK modulation technique.
2. BER versus SNR in AWGN channel for 16-QAM modulation scheme.
3. BER versus SNR in AWGN and multipath Rayleigh fading channel with Doppler
shift (60kmph, 90kmph and 120kmph) for QPSK modulation technique.
4. BER versus SNR in AWGN and multipath Rayleigh fading channel with Doppler
shift (60kmph, 90kmph and 120kmph) for 16-QAM modulation scheme.
5. BER versus SNR to compare between AWGN channel and multipath Raleigh
fading channel for different number of user for QPSK modulation technique.
6. BER versus SNR to compare between AWGN channel and multipath Raleigh
fading channel for different number of user for 16-QAM modulation technique.
Once data for BER and SNR under various parameters are obtained, the data are
tabulated. Graphs of BER as a function of SNR under different modulation
techniques as well as different velocities of mobile terminal subjected to noise and
interference channel will be plotted. These graphs will be studied and compared so
that a conclusion on suitable high data rate modulation scheme can be drawn.
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1.4 Scope of Work
This project is an entirely simulation project using scientific computer simulation
software, MATLAB 6.5.2. Two approaches will be used in this project. They are
simulation using Simulink and simulation using m files. It will be simulated in multi-
user environment based on Direct Sequence Spread Spectrum (DSSS), Wideband-Code
Division Multiple Access (W-CDMA). There will be no error correction coding or
channel coding employed for this simulation models.
There are two extreme cases of channel noise and fading that will be subjected
to the W-CDMA system models. Firstly, the model is simulated with different
modulation techniques under thermal noise, represented by Additive White Noise
Gaussian (AWGN). Then, the channel is simulated with various different parameters
using Non-Line of Sight (N-LOS) multiple reflected rays represented as multipath
Rayleigh fading.
The performance of the modulation schemes are studied when the mobile
terminal is static and mobile with different speeds. The performance measurement is
based on BER. Thus, suitable modulations techniques will be determined and concluded
based on BER that will be plotted as a function of function of SNR.
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1.5 Significant of the Project Research
The current trend to achieve high data rate cellular communication drives the
interest of this research. There are many ways one can improve data rate in a W-CDMA
system. However, two significant areas that could give significant boost to the
improvement of W-CDMA system is modulation scheme and error correction or channel
coding.
There are many modulation schemes that have the potential to deliver higher data
rate but there is a trade off between data rate and multipath environment. Modulation
techniques that can deliver more bits per symbol normally generate lots of error when
they are subjected to multipath channels. Recently, there is intensifying research about
Adaptive Modulation and Coding (AMC) [14]-[16]. The principle of AMC is to change
the modulation and coding format (transport format) in accordance with instantaneous
variations in the channel conditions, subject to system restrictions. AMC extends the
systems ability to adapt to good channel conditions. Channel conditions should be
estimated based on feedback from the receiver. For a system with AMC, users closed to
the cell site are typically assigned higher order modulation with higher code rates (e.g.
64 QAM with R=3/4 Turbo Codes). On the other hand, users closed to the cell boundary,
are assigned lower order modulation with lower code rates (e.g. QPSK with R=1/2
Turbo Codes). AMC allows different data rates to be assigned to different users
depending on their channel conditions. Since the channel conditions vary over time, the
receiver collects a set of channel statistics which are used both by the transmitter and
receiver to optimize system parameters such as modulation and coding, signal
bandwidth, signal power, training period, channel estimation filters, automatic gain
control, etc [3].
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Thus, this project will scrutinize suitable modulation techniques that are capable
to deliver highest data rate without compromising errors in multipath fading
environment. The performance of these modulation techniques will be simulated by
using computer simulation tool, MATLAB.
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CHAPTER 2
MODULATION SCHEMES IN WCDMA
The evolution of wireless cellular technology from 1G to 3G has a similar aim
that is capable to deliver high data rate signal so that it can transmit high bit rate
multimedia content in cellular mobile communication. Thus, it has driven many
researches into the application of higher order modulations [1]-[4] and [17]-[18].
The current second generation Global System for Mobile Communication (GSM)
system provides data services with 14.4 kbps for circuit-switched data and up to 22.8
kbps for packet data. High-Speed Circuit Switched Data (HSCSD) and General Packet
Radio Services (GPRS) with multi-slot operation can only slightly increase the data rate
due to the Gaussian Minimum Shift Keying (GMSK) modulation. Enhance Data Rate for
the GSM Evolution (EDGE) is proposed as a transition to 3G as a new Time Division
Multiple Access (TDMA) based radio access using the current (800, 900, 1800 and 1900
MHz) frequency bands. EDGE enables significantly higher peak rates and approximately
triples the spectral efficiency by employing 8-Phase Shift Keying (8PSK) modulation.
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WCDMA is another 3G-system operation in 5MHz bandwidth to support both
high-rate packet data and circuit-switched data. High Speed Downlink Packet Access
(HSDPA) is currently being developed as the evolution of WCDMA systems to
considerably increase the data rate by using adaptive modulation and coding (AMC),
hybrid automatic repeat request (HARQ), fast cell selection (FCS) and multiple input
multiple output (MIMO) antenna processing [4].
In cellular system, different users have different channel qualities in terms of
signal to noise ratio (SNR) due to differences in distance to the base station, fading and
interference. Link quality control adapts the data protection according to the channelquality so that an optimal bit rate is obtained for all the channel qualities [1-4]. Thus, the
system adopts AMC to suit the link quality. WCDMA systems can employ the high-
order modulation (8PSK or M-QAM) to increase the transmission data rate with the link
quality control.
However, there is a trade off in employing bandwidth efficient M-QAM
modulation scheme. The complexity of the receiver increases linearly with M (number
of orthogonal sequences) and exponentially with the number of bits per symbol. The
achievable bandwidth efficiency of the system is limited by the maximum possible
number of orthogonal sequences and by acceptable complexity of the receiver [2].
To minimize Inter-symbol Interference (ISI), noise and channel fading, a
wireless system needs to have a robust system to minimize, if not to eliminate, these
unfavorable effects. A typical W-CDMA transmitter system consists of bit generator, TC
encoder, rate matcher, interleaver, spreader, modulator, scrambler, and pulse shaper. On
the other hand, a receiver consists of a matched filter, channel estimator, rake receiver,
despreader, demodulator, deinterleaver, and TC decoder. Maximal ratio combining of
rake results amplitude boost is very favorable for M-PSK demodulation due to its greater
separation of the received symbol constellation. However, it is not the case for the M-
QAM. For an amplitude-modulated signal (M-QAM), amplitude change could produce
incorrect symbol detection [1].
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2.1 Bit Rate and Symbol Rate
To understand and compare different modulation format efficiencies, it is
important to understand the difference between bit rate and symbol rate. The signal
bandwidth for the communications channel depends on the symbol rate or also known as
baud rate.
symbolperdtransmittebitsofnumber
ratebitrateSymbol (1)
Bit rate is the frequency of a system bit stream. For example, a radio with an 8-
bit sampler is sampled at 10 kHz for voice. The bit rate, the basic bit stream rate in the
radio, would be 8 bits multiplied by 10k samples per second giving 80 kbps. In this
example, extra bits required for synchronization, error correction, etc are ignored for
simplicity. In GMSK, only one bit can be transmitted for each symbol. Thus, the symbol
rate for this modulation technique is 80 kbps. However, high data rate like 8-PSK, as it
will be reviewed in the next section, can transmit 3 bits per symbol. Thus, the symbol
rate, if this modulation scheme is employed, is 26.7 kbps. The symbol rate for 8-PSK is
three times smaller than that of GMSK. In other words, 8-PSK or any high order (M)
modulation scheme can transmit same information over a narrower piece of RF
spectrum.
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2.2 Quadrature Phase Shift Keying (QPSK)
QPSK is one example of M-ary PSK modulation technique (M = 4) where it
transmits 2 bits per symbol. The phase carrier takes on one of four equally spaced
values, such as 0, S/2, S and 3S/2, where each value of phase corresponds to a unique
pair of message bits as it is shown in figure 2.2. The basis signal for QPSK can be
expressed as
> @
-
tiEtiEts ssQPSK 21 1sin2
1cos IIS
i = 1,2,3,4
(3)
(1,1)
(-1,-1) (-1,1)
(1,-1)
Q
I
Figure 2.1: Constellation diagram of a QPSK system
Special characteristics of QPSK are twice data can be sent in the same bandwidth
compared to Binary PSK (BPSK) and QPSK has identical bit error probability to that of
BPSK. When QPSK is compared to that of BPSK, QPSK provides twice the spectral
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efficiency with the same energy efficiency. Furthermore, similar to BPSK, QPSK can be
differentially encoded to allow non-coherent detection.
Due to these advantages of QPSK, it has been employed as the modulation
technique in UMTS 3G wireless cellular networks where the following data rate can be
achieved depending on the channel quality.
i. 144 kbps for high mobility
ii. 384 kbps for low mobility
iii. 2 Mbps for indoor or static environment.
2.3 M-ary Quadrature Amplitude Modulation (QAM)
QAM is a modulation technique where its amplitude is allowed to vary with
phase. QAM signaling can be viewed as a combination of Amplitude Shift Keying
(ASK) as well as Phase Shift Keying (PSK). Also, it can be viewed as ASK in two-
dimension. Figure 2.2 shows the constellation diagram of 16-ary QAM (16-QAM). The
constellation consists of a square lattice of signal points. The general form of an M-ary
signal can be defined as
tfb
T
Etfa
T
Ets ci
s
ci
s
i SS 2sin2
2cos2 minmin (4)
Ttdd0 i = 1,2, .,M
where Emin is the energy of the signal with the lowest amplitude and ai and bi are a pair of
independent integers chosen according to the location of the particular signal point.
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Q
I
Figure 2.2: Constellation diagram of a 16-QAM system
Theoretically, higher order of M-ary QAM enables data to be transmitted in a
much smaller spectrum. However, the symbols are easily subjected to errors due to noise
and interference because the symbols are located very closed together in the
constellation diagram. Thus such signal has to transmit extra power so that the symbol
can be spread out more and this reduces power efficiency as compared to simpler
modulation scheme. Also the radio equipment is more complex.
2.4 Wideband-Code Division Multiple Access (W-CDMA)
2.4.1 Direct Sequence Spread Spectrum (DSSS)
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A DSSS system spreads the baseband data by directly multiplying the baseband
data pulses with a pseudo-noise sequence that is produced by a pseudo-noise (PN) code
generator [5]. A PN sequence is a binary sequence with an autocorrelation that
resembles, over a period, the autocorrelation of a binary sequence. Its autocorrelation
also roughly resembles the autocorrelation of band-limited white noise. The PN
sequence is usually generated using sequential logic circuits (i.e. feedback shift register).
A single pulse or symbol of the PN waveform is called chip. Spread spectrum signals are
demodulated at receiver through cross-correlation with locally generated version of the
pseudorandom carrier. Cross-correlation with the correct PN sequence de-spreads the
spread spectrum signal and restores the modulated message in the same narrow band asthe original data, whereas cross-correlating the signal from an undesired user results in a
very small amount of wideband noise at the receiver output.
Unlike modulation and demodulation techniques that have primary objective to
achieve power and/or bandwidth efficiency in AWGN channel, the transmission
bandwidth of DSSS has several orders of magnitude greater than the minimum required
signal bandwidth. In other words, DSSS modulation transforms an information signal
into a transmission signal with a larger bandwidth. It is achieved by encoding the
information signal with a code signal that is independent of the data and has a much
larger spectral width than that of information signal. In DSSS, many users can
simultaneously use the same bandwidth without significantly interfering one another.
DSSS is normally used in Code Division Multiple Access (CDMA) scheme.
The received DSSS signal for a single user can be represented as
TS tftptmT
Ets c
s
s
ss 2cos2
(5)
where m (t) is the data sequence, p (t) is the PN spreading sequence, fc is the carrier
frequency and is the carrier phase angle at t= 0.
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There are numerous advantages of DSSS for cellular radio system as they are
describe as follows:
1. DSSS has interference rejection capability since each user is assigned with a
unique PN code that is approximately orthogonal to the codes of other users.
2. Capable to resist radio jamming by a narrowband interferer.
3. DSSS eliminates the need of frequency planning since all cells can use the
same channels.
4. It has high resistance to multipath fading. Since DSSS signals have uniform
energy over large bandwidth, only a small portion of the spectrum will undergofading. The delayed version of PN sequence arrived at W-CDMA receiver will
have poor correlation with the original PN sequence and the receiver will
ignore it. This situation will occur even if the delay is only one chip form the
intended signal. In other words, the multipath signal would appear invincible to
the receiver.
5. Apart from resistance to multipath fading, DSSS can exploit the delayed
multipath components to improve the performance of the system. This can be
done by using RAKE receiver where it consists of a bank of correlators. Each
correlator will correlate to a particular multipath component of the desired
signal. The correlated outputs are weighted according to their strengths and
summed to obtain the final signal estimate.
Two conditions have to be satisfied for a technique to be classified as a spread spectrum
technique.
1. The transmission bandwidth must be larger than the information bandwidth.
2. The resulting radio-frequency bandwidth must be determined by a function
other than the information being sent. This excludes such modulation
techniques such as frequency modulation (FM) and (PM).
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2.4.2 Code Division Multiple Access (CDMA)
CDMA is a multiple access scheme employed normally with DSSS. Each user
has a unique code that is orthogonal to one another. In CDMA, the power of multiple
users at a receiver determines the noise floor after decorrelation. CDMA can be viewed
with a figure 4.4 as it is shown below.
Code
Frequency
Channel 1
Channel 2
Channel 3
Channel N
Time
Figure 2.3: CDMA
2.5 Noise and Interference
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2.5.1 Additive White Noise Gaussian (AWGN)
The term noise refers to unwanted electrical signals that are always present in
electrical systems [6]. The term additive means the noise is superimposed or added to the
signal that tends to obscure or mask the signal where it will limit the receiver ability to
make correct symbol decisions and limit the rate of information transmission. Thus,
AWGN is the effect of thermal noise generated by thermal motion of electron in all
dissipative electrical components i.e. resistors, wires and so on [6]. Mathematically,
thermal noise is described by a zero-mean Gaussian random process where the random
signal is a sum of Gaussian noise random variable and a dc signal that is
z= a + n (6)
where pdf for Gaussian noise can be represented as follows where 2 is the variance ofn.
2
2
1exp
2
1)(
VSV
azzp (7)
A simple model for thermal noise assumes that its power spectral density Gn(f) is
a flat for all frequencies and is denoted as
2)( 0
NfGn (8)
where the factor of 2 is included to indicate that Gn(f) is a two-sided power spectral
density. When noise power has such a uniform spectral density, it is referred as white
noise. The adjective "white" is used in the same sense as it is with white light, which
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contains equal amounts of all frequencies within the visible band of electromagnetic
(EM) radiation.
Since thermal noise is present in all communication systems and is a prominent
noise source for most system, the thermal noise characteristics that are additive, white
and Gaussian are most often used to model the noise in communication systems.
2.5.2 Rayleigh Fading
Since signal propagation takes place in the atmosphere and near the ground, apart
form insignificant effect of free path loss, Ls, the most notable effect of signal
degradation is multipath propagation. The effect can cause fluctuations in the received
signal's amplitude, phase and angle of arrival, giving rise to terminology multipath
fading[7].
Generally, there are two fading effects in mobile communications: large-scale
and small-scale fading. Large-scale fading represents the average signal power
attenuation or path loss due to motion over large areas. On the other hand, small-scale
fading refers to the dramatic changes in signal amplitude and phase that can be
experienced as a result of small changes (as small as a half-wavelength) in the spatial
separation between a receiver and transmitter. Small-scale fading is also called Rayleigh
fading because the envelope of received signal can be represented by a Rayleigh pdf [7].The received signal consists of large number of multiple reflective paths and there is no
line-of-sight signal component. When there is a dominant non-fading signal component
present, such as a line-of-sight propagation path, the small-scale fading envelope is
described by a Rician pdf [5].
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Figure 2.4: Relationship among channel correlation function
and power density function
TheDoppler spread is a measure of the spectral broadening due to the time rate
of change (time variant) of the channel parameters. Figure 2.4 (d) shows a Doppler
power spectral density, S(v), plotted as a function of Doppler-frequency shift, vbased on
dense-scatterer channel model. For the case of the dense-scatterer model, a vertical
receive antenna with constant azimuthally gain, a uniform distribution of signals arriving
at all arrival angles throughout the range (0,2p), and an unmodulated continuous wave
(CW) signal, the signal spectrum at the antenna terminals is
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2
1
1)(
dd f
vf
vS
S
(9)
where fd is Doppler Spread andfc carrier frequency. The largest magnitude (infinite) of
S(v) occurs when the scatterer is directly ahead of the moving antenna platform or
directly behind it. Thus, from this situation, the magnitude of the frequency shift is given
by
OVfd (10)
where V is relative velocity and O is the signal wavelength. fd is positive when the
transmitter and receiver move towards each other, and negative when moving away from
each other. Equation 10 describes the Doppler frequency shift. In a typical multipath
environment, the received signal arrives from several reflected paths with different path
distances and different angles of arrival, and the Doppler shift of each arriving path is
generally different from that of another path. The effect on the received signal is seen as
a Doppler spreading or spectral broadening of the transmitted signal frequency, rather
than a shift. The Doppler power spectral density is infinite for Doppler components that
arrive at exactly 0q and 180q. Thus the angle of arrival is continuously distributed and
the probability of components arriving at exactly these angles is zero.
2.6 Bit Error Rate (BER)
BER is a performance measurement that specifies the number of bit corrupted or
destroyed as they are transmitted from its source to its destination. Several factors that
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affect BER include bandwidth, SNR, transmission speed, transmission medium and
transmission speed.
2.7 Signal-to-Noise Ratio (SNR)
SNR is defined as the ratio between signal power to noise power and it is
normally expressed in decibel (dB). The mathematical expression of SNR is
dBpowernoise
powersignalSNR log10 (11)
2.8 DSSS-CDMA Bit-Error Probability Calculations
There are two approaches to calculate BER for DSSS-CDMA operating under
AWGN channel [8]-[10]. The first approach uses accurate BER approximations because
it is presumed that BER evaluation is numerically cumbersome. There are many
researches on this approach and most widely used approximation is the so-called
Standard Gaussian Approximation (SGA) [8]-[10]. In the SGA, a central limit theorem
(CLT) is employed to approximate the sum of the multiple-access interference (MAI)
signals as an AWGN process additional to the background Gaussian noise process. To
detect desired user signal, the receiver design consists of a conventional single-user
matched filter (correlation receiver). The average variance of the MAI over all possible
operating conditions is used to compute the SNR at the filter (correlator) output. SGA is
widely used because it is easy to apply. However, it is known based on performance
analysis that SGA often overestimate system performance especially for small number of
users. Thus, Improved Gaussian Approximation (IGA) is created to overcome the
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)cos()()(2 kckkkk twtabtPs T (12)
where Pk represents transmitted signal power, bk(t) is data signal, ak(t) is spreading
signal, wc is carrier frequency and k is carrier phase. The kth users data signal is a
random process that is a rectangular waveform, taking values from with service rate, and
is expressed as
)()()(
jTtPbtb Tk
j
j
k
f
f
(13)
where PT(t) = 1, for Ttdd0 , andPT= 0, otherwise. Thejth data bit ofkth
user is
denoted as bj(k)
. Data source are assumed uniform, i.e.
2/111)()( kjr
k
jr bPbP . The spreading signal ak(t) can be expressed as
)()()(
lTtatak
l
l
k
f
f
\ (14)
where (t) is an arbitary chip waveform that is time-limited to [0,Tc) and Tc is chip
duration. Chip waveform is assumed to be normalized according to cT
Tdttc
)(02\ .
The lth
chip of the kth
user is denoted al(k)
, which assumes values from {-1,+1}. All
signature sequences {ak(k)
}are assumed to be random in the following sense. Every chip
polarity is determined by flipping an unbiased coin. Further justification for the random
chip sequence assumption is provided in. There areNchips for one data symbol and the
period of the signature sequence is N. We normalize the chip duration so that Tc=1 and,
thus, T=N. Note that if the chip waveform is rectangular, i.e.,
)()()(
cT
k
jjkjTtPata
c
f
fthe transmitted signal becomes the well-known phased-
coded SS model [9].
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For QPSK modulation scheme, the transmitted signal of kth
user in the sub-
system i is
)cos()()(2)cos()()(2)( ikcQ
ik
Q
ikiikc
I
ik
I
ikiik ttctbPttctbPts TZTZ (15)
where )(tbIik and )(tbQ
ik are the In-phase and Quadrature-phase signal.
2.9.2 Receiver Model
The received signal r(t) at the input of the matched filter receiver is given by
)()cos()()(2)()()(11
tnttatbAPtnthstr kckkkkkk
K
k
kk
K
k
u
IZWW
(16)
where * denotes convolution and kckkk WZTEI is assumed a uniform random
variable over [0, 2). The average received power of the kth
signal isE[Pr] =E[A
2k]Pk.
2.9.3 Channel Model
2.9.3.1 AWGN
The transmitted signal for BPSK modulation is subjected to AWGN process n(t),
that has two-sided power spectral densityN0/2 andAk= 1, k=1, .,K. Ak is independent,
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Rayleigh-distributed and account for the fading channel attenuation of all signal. The
first order of probability density function (pdf) is given by
)()( ),0[2/2 aIaeaP aAk f
(17)
Due to the fact that SGA considers an average variance value for Multi Access
Interference (MAI) or in other words, the first moment of, the IGA exploits knowledge
of all moments of. It was shown in [19] that the BER for an AWGN channel obtained
from IGA is significantly more accurate than the BER obtained from the SGA especially
for small number of user, k. Thus by applying SIGA, overall BER can be represented as
[13]
|
222 31
12
1
31
12
11
3
1
N
N
N
N
N
NP
SIGA
e
]]]] VPVPP]
(18)
where and 2
are given by
)1(3
2 K
N]P (19)
and
9
1)2(181843
45
1)1( 2
2 NKNNK]V (20)
where this Holtzmans method is extended by applying first and second moment for the
received power.
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2.9.3.2 Rayleigh Fading
The output of a low pass filter (LPF) of a synchronous system i.e. W1 = W2 = =
Wkfor user 1 can be represented as
111
011 )cos()()(
nIS
dttwtatry cT
(21)
where n1 is a zero-mean Gaussian random variable with variance 4/02
1NNn V , S1 is
the signal component NAS 11 r , and the interference termI1 is given by
dttatabAIT
kk
kk
k
k )()()cos( 10
)(
0
2
1
I (22)
Since a sum of independent Gaussian random variable has Gaussian distribution, it
follows that I1 is a Gaussian random variable with zero-mean and
variance 212
22
1 k
K
k
I N UV
. By symmetry and using the independenceI1 and n1, one has
K
k k
SSYNC
Ae
NNN
NAQP
2
2
1
20
1
4
1
U
(22)
and averaging over the pdf of A1, BER for a Rayleigh-faded user is
K
k k
SYNC
e
N
NP
2
2
1
0
41
11
2
1
U
(23)
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From the equation above, one sees that the interferers act like additional independent
Gaussian background noise. This is because the MAI on the flat Rayleigh fading channel
has a Gaussian first-order distribution assuming synchronous transmission. This implies
that the optimum receiver that does not perform user-interference cancellation is a
correlator detector. However, this is not the case of asynchronous transmission. For
uniformity, uniform random signature sequences NE k /1][2
1 U and
NK
NN
PSYNCe
14
1
11
2
1
0
(24)
In asynchronous transmission subjected to flat Rayleigh fading, average BER is
computed by using characteristic function, ). The proof for the following characteristic
function can be found in [8]. Average characteristic function of MAI Ik, given B, is
> @),1()1,()1,(,14
2
)()(
22
)1(
,
jiJjiJjiJjiJ
dSBS
B
Bj
Bj
A
Ai
Ai
N
kkBSI kk
u
))
ZZ
(25)
Using the fact that theIk's given B are independent, the characteristic function for
total interference termI, given B, is
))K
k
BIBI k2
)()( ZZ (26)
The conditional BER for target user, after averaging over pdf ofA1, can be expressed by
symmetry as
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> @ ZZZZSV dNN
NP nBI
n
Be
-u))
22
22 2
1exp)()(12
112
11
1
(27)
When the effect of background noise is negligible, 021|nV and 11 |) n , thus equation
27 becomes
> @
ZZZS
ZZZZ
SdN
N
dNN
P
BI
nBIBe
-)
-u))
f
f
22
0
22
0
2
1exp)(
22
1
2
1exp)()(1
21
(28)
Equation (26), (27), and (25) [or (26), (28) and (25) for noiseless case] give the
average BER experience by a target user with a signature sequence that has a given
value of B. The average BER for all users of for one target user averaged over all
signature sequences randomly assigned by a base station for each request is
Be
N
B
N
B
N
e PP
1
0
1)1(2 (29)
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CHAPTER 3
CONFIGURATIONS ON WCDMA SYSTEM
The research project is started with literature review on high data rate modulation
schemes, DSSS, W-CDMA, and fading effects on channel. Then, a generic model of
DSSS W-CDMA as it is shown in figure 3.1 is simulated using QPSK and it is followed
by QAM. QPSK and QAM are chosen in this project because there are the primary
candidates to deliver higher data rate for High Speed Downlink Packet Access
(HSDPA), an extension of 3G networks [14]-[16]. The simulation is done under noise
and multipath fading channel using MATLAB 6.5.2.
As it is shown in figure 3.1, the user data is assumed to be Bernoulli distributed
and it is represented as bn(t). Each user data is then multiplied with independent ordifferent PN code produced by a PN generator using XOR logical operator. The
multiplied signal of each user is represented as sn(t) after the signal is modulated by
either QPSK or QAM. Each signal is added before it is subjected to the channel. At the
receiver, the signalsk(t) is demodulated before the user data is separated from PN code
by XOR logical operator. Finally, when the necessary simulations are done, tables and
graphs of BER as a function of SNR for various parameters are plotted. Analysis,
comments and conclusion will be drawn based on the simulation results.
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AWGN and Rayleigh fading are chosen to represent fading effect in the channel
because we want to make a comparison of WCDMA system models in two extreme
channel conditions. There are many fading effects that can be categorized as large-scale
and small-scale fading. Rayleigh fading represents the worst case of multipath fading
where it represents small-scale fading due to small changes in position. On the other
hand, AWGN represents the thermal noise generated by electrical instruments.
3.1 Simulation Methodology
Computer simulation is the most suitable, powerful and efficient way to represent the
actual or real situation of mobile radio system. Thus, MATLAB 6.5.2 has been identified
to simulate W-CDMA model based on related theories, formulae and parameters. Two
approaches are adopted in this project. Firstly, the simulation is simulated using
Simulink and it follows with simulation using m files. Throughout this project, the bit
rate for the signal generator is 384kbps.
There will be three WCDMA wireless cellular system models that will be used in
this project. The models are
1. WCDMA system in AWGN channel
2. WCDMA system in AWGN and Multipath Rayleigh Fading.3. Multi-user WCDMA system in AWGN and Multipath Rayleigh Fading.
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WCDMA system in
AWGN
WCDMA system in
AWGN and multipath
Rayleigh fading
Multi-user WCDMA systemin AWGN and multipath
Rayleigh fading
QPSK
16-QAM
QPSK
16-QAM
QPSK
16-QAM
Stage 1
Stage 2
Stage 3
Test
Simulation
Check
for any
errors
Performance
analysis: BER
& SNR
Continue next
subsequent
stage
Figure 3.1: Simulation flow chart for W-CDMA system models used in Simulink and M
files
3.2 Simulation Using Simulink
Two types of simulation have been chosen to study the performance of
modulation techniques of WCDMA subjected to multipath fading in the channel. The
project begins with simulation using simulink. Simulink is a software package that has
the capabilities to model, simulate, and analyze dynamic systems whose outputs and
states change with time. Simulink can be used to explore the behavior of a wide range of
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real-world dynamic systems making it suitable computer software to study the
performance of modulation techniques under multipath fading. Simulating a dynamic
system is a two-step process with Simulink. First, a graphical model of the system is
simulated, using the Simulink model editor. The model depicts the time-dependent
mathematical relationships among the system's inputs, states, and outputs. Then,
Simulink is used to simulate the behavior of the system over a specified time span.
Simulink uses information entered into the model to perform the simulation.
3.2.1 Simulation in Phase 1: WCDMA System in AWGN Channel
In Phase 1, both transmitter and receiver part are built based on the system model as
shown in Figure 3.5. The channel is subjected to AWGN only. This phase is divided
into five parts as follows:
1. Assumptions
2. Transmitter part
3. Receiver Part
4. Channel Part
5. Performance Analysis
3.2.1.1 Assumptions in Phase 1
The assumptions made for this phase of simulation are stated as follows:
x Evaluation of the performance is made on one user in the multi-user
environment. It considers the rest of the users contribute the multi user
interference to the reference user in the system.
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x Decision statistic of the receiver, Z0 is modeled as Gaussian Random
Variable.
x Decision statistic of the desired user, I0 is deterministic.
x Multi-User Interference (MUI), ] in the system is assumed as zero-mean
Gaussian variables and it is an AWGN. This is based on the ARIB
proposal which states that all interference from other users is modeled as
Additive White Gaussian Noise (AWGN).
x Thermal noise K is very small and negligible. This is based on the data in
ARIB proposal.
x In this simulation, only downlink (base station to mobile station)transmissiont is considered.
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F
igure3.2:W-CDMAModelusingQPSKmodulationtechnique
inAWGNchannel
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Figure3.3:W
-CDMAModelusing16-QAM
modulationtechniqueinAWG
Nandmultipathfadingchannel
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3.2.1.2 Transmitter Design
3.2.1.2.1 User Data Sequence Generator
The signal is produced by Bernoulli Data Generator. The Bernoulli Binary
Generator block generates random binary numbers using a Bernoulli distribution. The
Bernoulli distribution with parameter p produces zero with probability p and one with
probability 1-p. The Bernoulli distribution has mean value 1-p and variance p(1-p). The
Probability of a zero parameter specifies p, and can be any real number between zeroand one. Table below shows the parameters used in Bernoulli Binary Generator block.
Table 3.1: Parameters for Bernoulli Binary Generator Block
Parameter Value
Probability of Zero 0.5
Initial Seeds 12345
Sample Time Tsample
Frame-based Output unchecked
Interpret Vector Parameter as 1-D unchecked
Parameters for Bernoulli Binary Generator Block
Probability of Zero: The probability with which a zero output occurs. The value
of 0.5 means the random binary numbers generated having equal amount of 0
and 1.
Initial Seeds: The initial seed value for the random number generator. 12345 has
been chosen.
Sample Time: The period of each sample-based vector or each row of a frame-
based matrix. Here, Tsample is declared in the associated m file
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(chk_QPSK_no_noise.m) and it has a value of 1/384000 seconds or an inverse of
bit rate of 384 kbps.
Attribute of Output Signal. In this block, we declare the signal to be sample-
based where the frame-based outputs box is unchecked.
3.2.1.2.2 Spreading Sequence Generator
The PN Sequence Generator block generates a sequence of pseudorandom binary
numbers. A pseudo-noise sequence can be used in a pseudorandom scrambler and
descrambler. It can also be used in a direct-sequence spread-spectrum system. The PN
Sequence Generator block uses a shift register to generate sequences. Table 3.2 below
shows the parameter that has been used in the simulation.
Table 3.2: Parameters used in PN Sequence Generator Block
Parameter Value
Generator Polynomial [1 0 0 0 0 1 1]
Initial States [1 0 0 0 0 1]Shift (or mask) 0
Sample time, Tc Tchip
Attribute of Output Signal Sample-based output
Parameters Specific to PN Sequence Generator
a) The Generator polynomial parameter has been specifying using this format:
x A vector that lists the coefficients of the polynomial in descending order
of powers. The first and last entries must be 1. Note that the length of this
vector is one more than the degree of the generator polynomial.
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It is known that the degree of the generator polynomial is 6 so the length of the vector is
7. So, in this simulation, the value of Generator Polynomial specifies as [1 0 0 0 0 1 1]
represent the same polynomial, p (z) = z6 + z1 + 1 to fulfill the format above.
b) The initial states parameter is a vector specifying the initial values of the
registers. The initial states parameter must satisfy these criteria:
x All elements of the Initial states vector must be binary numbers.
x The length of the Initial states vector must equal the degree of the generator
polynomial.
x At least one element of the Initial states vector must be nonzero in order for theblock to generate a nonzero sequence. That is, the initial state of at least one of
the registers must be nonzero.
So, in this simulation, the value of initial states specifies as [1 0 0 0 0 1] to satisfy the
criteria above.
c) Sample time, Tc in this case is equal to chip period. In this simulation chip
period 260.4167 ns inverse of chip rate, 3.84 M chips per second (Mcps) is used and it is
declared in the chk_QPSK_no_noise.m file. In the sample time parameter check box of
the QPSK_no_noise.mdl file, it is declared as Tchip.
d) Attribute of Output Signal.
In Simulink, each matrix signal has a frame attribute that declares the signal to be
either frame-based or sample-based, but not both. (A one-dimensional array signal is
always sample-based, by definition.) Simulink indicates the frame attribute visually by
using a double connector line in the model window instead of a single connector line. In
general, Simulink interprets frame-based and sample-based signals as follows:
x A frame-based signal in the shape of an M-by-1 (column) matrix represents M
successive samples from a single time series.
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x A frame-based signal in the shape of a 1-by-N (row) matrix represents a sample
of N independent channels, taken at a single instant in time.
x A sample-based matrix signal might represent a set of bits that collectively
represent an integer, or a set of symbols that collectively represent a code word,
or something else other than a fragment of a single time series.
So, in this block, we declare the signal to be sample-based with unchecked the frame-
based outputs box.
3.2.1.2.3 Spreader
XOR block has been used to operate like a spreader. Spreader causes the data
symbols to be spread to a higher bandwidth, by multiplying the random binary data
symbols, bit rate equal to Tb with a high bit rate code sequence (pseudo noise chip
sequence), chip rate equal to Tc.
Parameters Specific to Logical Operator Block
a) Operator. XOR has been selected.
b) Number of input ports = 2
c) Show additional parameters box is checked.
d) Require all inputs and output to have same data type box is checked.
e) Output data type mode. Logical has been selected. To avoid any data or signal
incompatibility, the following steps are taken. Go to the menu bar of
simulation/simulation parameters/Advanced tab. Select Boolean Logic Signals to off,
then the output data type will match the input data type, which may be Boolean or
double.
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3.2.1.3 Modulation Techniques
3.2.1.3.1 QPSK Modulator
In this simulation, Quadrature Phase Shift Keying (QPSK) Passband modulator
has been used. The M-PSK Modulator Passband block modulates using the M-ary phase
shift keying method. The output is a passband representation of the modulated signal.
The M-ary number parameter, M, is the number of points in the signal constellation.
This block uses the baseband equivalent block, M-PSK Modulator Baseband, forinternal computations and converts the resulting baseband signal to a passband
representation. The following parameters in this block are the same as those of the
baseband equivalent block:
x M-ary number
x Input type
x Constellation ordering
The input must be sample-based. If the Input type parameter is Bit, then the input
must be a vector of length log2 (M). If the Input type parameter is Integer, then the input
must be a scalar.
This block uses a baseband representation of the modulated signal as an intermediate
result during internal computations.
Table 3.3 below shows the parameter that has been used in the simulation.
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Table 3.3: Parameters used in QPSK Modulator Passband Block
Parameter Value
M-ary number 4
Input type Integer
Symbol period (s) 1 / 3840000 Hz
Baseband samples per symbol 1
Carrier frequency (in Hz) 15000000
Carrier initial phase (in rad) pi/4
Output sample time (s) 1 / 38000000 Hz
Parameters Specific to Passband Simulation
a) M-ary number is set up to 4 means it using four points in the signal
constellation. This setting also indicates the modulator to function as a QPSK modulator.
b) Input type parameter is set up to integer means the input must be a scalar.
c) The Symbol period parameter must equal the sample time of the input signal.
The sample time of the input signal is equal to Tc = 260.4167 ns. So, the symbol period
equal to 260.4167 ns or inverse of 1/3840000 Hz.
d) Baseband samples per symbol. The Baseband samples per symbol parameter
indicates how many baseband samples correspond to each integer or binary word in the
input, before the block converts them to a passband output. In this simulation, baseband
samples per symbol specify to one baseband sample per symbol.
e) Passband simulation uses a carrier signal. Carrier frequency (fc), 15,000,000
Hertz (Hz) has been used. The actual carrier frequency that should be used is 2 GHz to
fulfill the third generation requirements. Smaller frequency is used because of the
computer ability to simulate larger value of the carrier frequency. Simulation runs very
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slow when value 2 GHz applied. The assumption made for simulation environment, the
differences between values of carrier frequency does not affect the system.
f) Carrier initial phase in radians specify the initial phase of the carrier signal. In
this simulation, the initial phase = (pi/4) or S/4 indicates the initial phase for QPSK
modulation scheme.
g) Output sample time. The Output sample time parameter determines the sample
time of the output signal. The timing-related parameters must satisfy these
relationships:x Symbol period > (Carrier frequency)-1
x Output sample time < [2*Carrier frequency + 2/(Symbol period)]-1
Furthermore, Carrier frequency is typically much larger than the highest frequency of the
unmodulated signal.
First Condition = Symbol period > (Carrier frequency)-1
Symbol period = 260.4167 ns
Carrier frequency (fc) = 15,000,000 Hz
[Carrier frequency (fc)]-1 = 66.667 ns
So, 260.4167 ns > 66.667 ns, satisfy first condition
When first condition satisfied, the value of output sample time should satisfy the second
condition.
Output sample time < [2*(15,000,000 Hz) + 2 / (260.4167 ns)]-1
Output sample time < [30 MHz + 7.68 MHz]-1
Output sample time < 26.54 ns
So, in this simulation, the output sample time has been determined to 26.32 ns or inverse
of1 / 38,000,000 Hz.
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3.2.1.3.2 16-QAM Modulator
Same design procedures are implemented for 16-QAM modulator. Table below
shows the parameters used in rectangular 16-QAM modulator passband block.
Table 3.4: Parameters used in M-QAM modulation block
Parameter Value
M-ary number 16
Input type Integer
Normalized method Min. Distance between symbols
Minimum distance 2
Symbol period 1/100
Baseband samples per symbol 1
Carrier frequency (Hz) 15e6
Carrier Initial Phase (rad) 0
Output Sample Time 1/38e6
Normalization method determines how the block scales the signal
constellation.
Minimum distance is the distance between two nearest constellation points.
Symbol period (s) is the symbol period, which must equal the chip sample
time of the PN sequence generator
Baseband sample per symbol is the number of baseband samples that
correspond to each integer or binary word in the input, before the block
converts them to a passband output.
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3.2.1.4 Channel Design
The following table 3.5 shows the parameters used in AWGN block.
Table 3.5: Parameters used in AWGN block
Parameter Value
Initial seeds 1237
Mode Signal to Noise ratio (Es/No)
Es/No EbNo
Input Signal Power (Watt) 1
Symbol-period (s) Tchip
In the generic m file, the EbNo will produce a sequence of 2 EbNo intervals for
12 EbNo. The symbol period of AWGN block is Tchip that is equivalent to 1/38e6.
3.2.1.5 Receiver Design
3.2.1.5.1 QPSK Demodulator
The M-PSK Demodulator Passband block demodulates a signal that was
modulated using the M-ary phase shift keying method. The input is a passband
representation of the modulated signal. The M-ary number parameter, M, is the number
of points in the signal constellation. This block converts the input to an equivalent
baseband representation and then uses the baseband equivalent block, M-PSK
Demodulator Baseband, for internal computations. The following parameters in this
block are the same as those of the baseband equivalent block:
x M-ary number
x Output type
x Constellation ordering
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The input must be a sample-based scalar signal. Similar parameters for QPSK
Demodulator will be used as QPSK Modulator except for parameter input sample time.
In this simulation, input sample time is equal to output sample time of QPSK Modulator.
Table3.6 below shows the parameter that has been used in the simulation.
Table 3.6: Parameters used in QPSK Demodulator Passband Block
Parameter Value
M-ary number 4
Input type IntegerSymbol period (s) 1 / 3840000 Hz
Baseband samples per symbol 1
Carrier frequency (in Hz) 15000000
Carrier initial phase (in rad) pi/4
Input sample time (s) 1 / 38000000 Hz
Delays from QPSK Demodulation
Digital modulation and demodulation blocks sometimes incur delays between
their inputs and outputs, depending on their configuration and on properties of their
signals. Refer to the Release Notes Communication Blockset for Use with Simulink,
all passband demodulators except OQPSK will experience delays in amount of one
output period. So, QPSK passband demodulator causes delays of one ouput period occur
in this simulation block.
To calculate the bit error rate correctly, additional delay of 1 second to the
transmitted signal to synchronize it with the received signal. This is done directly in the
mask for the Error Rate Calculation block by setting the Receive delay to 1.
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For the same reason, the PN chip sequence and received signals need to be
synchronizing before they enter the Despreader block. In this case, Integer Delay block
has been used, which delays a signal by the number of sample periods specified by the
Delay parameter. Set the Delay to 1. This is indicated by the exponent -1 on the block.
The delay synchronizes the PN chip sequence signal with the received signal so that the
Despreader block can recovered back the original data symbols correctly.
16-QAM Demodulator
As in QPSK demodulator, similar design procedure will be employed for 16-QAM. Table below shows the parameters used in rectangular 16-QAM Demodulator
block. The parameters are the same parameters used in initializing the parameters in 16-
QAM modulator block.
Table 3.7: Parameters used in 16-QAM Demodulator Passband Block
Parameter Value
M-ary number 16
Input type Integer
Normalized method Min. Distance between symbols
Minimum distance 2
Symbol period 1/100
Baseband samples per symbol 1
Carrier frequency (Hz) 15e6
Carrier Initial Phase (rad) 0
Output Sample Time 1/38e6
3.2.1.6 Despreader
In order to recover the data symbols from the spreading signal, the process of
dispreading is applied. This is done by XOR the high bit rate noise-like signal with a
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local spreading chip code that has the same sequence with the transmitting code. When
this right code is chosen with right synchronization, in this case delay is one output
period; the output from the XOR block will be exactly the same as the source signal.
Parameters for Despreader block are same like the Spreader block.
3.2.1.7 Error Rate Calculation
The Error Rate Calculation block compares input data from a transmitter with
input data from a receiver. It calculates the error rate as a running statistic, by dividing
the total number of unequal pairs of data elements by the total number of input dataelements from one source.
Table 3.8 below shows the parameter that has been used in the simulation.
Table 3.8: Parameters used in Error Rate Calculation Block
Parameter Value
Receive delay 1
Computation delay 0
Computation mode Entire frame
Output data Port
Reset port box Unchecked
Stop simulation box Checked
Target number of errors 5000
Maximum number of symbols 5000
a) Receive delay set up to 1 due to delay causes by QPSK Demodulator. Refering
to the release notes Communication Blockset for Use with Simulink, the delay should
be put as 1 to ensure the transmitted signal synchronize with the received signal.
b) Computation mode is set to entire frame. Then the block compares the entire
transmitted frame with the entire received frame.
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c) Output Data. This block produces a vector of length three, whose entries
correspond to:
x The error rate.
x The total number of errors, that is, comparisons between unequal elements.
x The total number of comparisons that the block made.
Output data parameter is set to Port, and then an output port appears. This output port
contains the running error statistics. Output port from this block connected to the
Display.
d) The simulation stops when the maximum number of symbols is reached at 5000
data symbols even the target number of errors not reached 5000 errors.
3.2.1.8 Display
The Display block shows the value of its input, the amount of data displayed and the
time steps at which the data is displayed are determined by block parameters:
x The display format can be control by selecting a Format choice: short, which
displays a 5-digit scaled value with fixed decimal point
x The Decimation parameter enables you to display data at every nth sample,
where n is the decimation factor. The default decimation, 1, displays data at
every time step.
x The Sample time parameter enables you to specify a sampling interval at which
to display points. This parameter is useful when you are using a variable-step
solver where the interval between time steps might not be the same. The default
value of -1 causes the block to ignore the sampling interval when determining the
points to display.
Table 3.9 below shows the parameter that has been used in the simulation.
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Table 3.9: Parameters used in Display Block
Parameter Value
Format Short
Decimation parameter 1
Floating display cox unchecked
Sample time -1
The display block shows the bit error rate, the number of errors and the total number of
bits that are transmitted.
3.2.1.9 Performance Analysis for Phase 1
In this simulation, a generic m file is used together with simulink to simulate the
BER vs Eb/No graphs (refer to Appendix, section 1.1). This m file declares the
parameters defined in the simulinks block diagram check box. For example, variable
Tsample declared in the m file is the sampling time of Bernoulli Binary Generator.
Tchip, on the other hand, is the sampling time of spreading sequence generator.
EbNoVec is signal to noise ratio and it is taken at 6 evenly points starting from 0. Then,
for loop is used to calculate the BER for every EbNoVec assigned to it. The value of
EbNo will be stored in the work space. Commandsim is used to simulate simulink mdl
file. Finally, commandsemilogis used to create the graph for BER vs Eb/No.
First, the simulation is done by running the concerned mdl file. Once the output
values are stored in the workspace, the associated m file is typed under the command
window and it is run. Finally, BER graph vs EbNo graphs are obtained once the
simulation is completed.
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The generic m file used to generate BER vs Eb/No graph
M = 4;
Tsample = 1/384000; % Bernoulli Binary Sampling time
Tchip= 1/3840000; % Chip sampling time
BERVec = [];
EbNoVec = [0:2:12];
for n=1:length(EbNoVec);
EbNodB = EbNoVec(n);
sim('WCDMA_QPSK_baseband');
BERVec(n,:) = BER;
end;
semilogy(EbNoVec,BERVec(:,1),'+');
legend('Bit error rate');
xlabel('Eb/No (dB)'); ylabel('Error Probability');
title('Bit Error Probability');
In this phase, the system is simulated based on the following conditions
1. Bit Error Rate (BER) versus Signal-to-Noise ratio (SNR) in AWGN channel for
QPSK modulation technique.
2. BER versus SNR in AWGN channel for 16-QAM modulation scheme.
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3.2.2 Simulation Phase 2: WCDMA system in AWGN and Multipath Rayleigh
Fading
In Phase 2, both transmitter and receiver part are built based on the system model
as shown in figure 3.2 and figure 3.3. In this model, multipath Raleigh fading channel
block is added in the system. The rest of system blocks and parameters are unchanged.
In this phase of simulation, the model is simulated in the baseband simulation
environment. The input of multipath Raleigh fading block requires complex signal
which can be obtained through baseband simulation only.
Moreover, in passband simulation, the simulation models the carrier frequency.
Since the carrier frequency is usually a high frequency signal, modeling passband
communication systems involves high computational loads. To alleviate this problem,
baseband simulation techniques are used.
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Figure3.4:W-C
DMAModelwithmultipathRa
leighfadingchannelandAWGNchannelusingQPSKModulation
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Figure
3.5:W-CDMAModelusing16-QAMinAWGNandmultipathRaleighfadingchannel
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3.2.2.1 Channel
Table 3.10 below is used to initialize the parameters in the multipath Rayleigh fading
block.
Table 3.10: Parameters used in multipath Rayleigh fading channel
Parameter Value
Maximum Doppler shift (Hz) 55.56 / 83.33 / 111.111
Sample time (s) 1/3840000Delay vector (s) 2-ray [0 2e-6]
3-ray [0 2e-6 3e-6]
Gain vector (s) 2-ray [0 -3]
3-ray [0 -3 1]
Normalize gain vector to 0 dB overall gain box Checked
Initial seed 40
a) Maximum Doppler shift (Hz). Relative motion between the transmitter and
receiver causes Doppler shifts in the signal frequency. The Jakes PSD (power spectral
density) determines the spectrum of the Rayleigh process. This implementation is based
on the direct form simulator described in reference [1]. Some wireless applications, such
as standard GSM (Global System for Mobile Communication) systems, prefer to specify
Doppler shifts in terms of the speed of the mobile. If the mobile moves at speed v
making an angle T of with the direction of wave motion, then the Doppler shift is
Tcos
c
vfFd (3.20)
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where f is the transmission carrier frequency and c is the speed of light. The Doppler
frequency is the maximum Doppler shift arising from motion of the mobile.
In this project, to determine maximum Doppler shift for third generation systems,
we assume that the transmission carrier frequency, f = 2GHz. We assume mobile moves
at three different speed, v = 60 km/hr, v = 90 km/hr and v = 120 km/hr. Different speeds
modeling the system in three different situations; in the middle of town, in the main road
and in the highway. Angle T set to 60 degree.
Based on the assumptions above, the maximum Doppler shift for every speed value is:
When v = 60 km/hr;
HzFd
ms
GHzhrkmFd o
56.55
60cos103
2/6018
u
u
(3.20(a))
When v = 90 km/hr;
HzFdms
GHzhrkmFd o
33.83
60cos
103
2/9018
u
u
(3.20(b))
When v = 120 km/hr;
HzFd
ms
GHzhrkmFd o
111.111
60cos103
2/12018
u
u
(3.20(c))
b) Sample time equal to chip code rate, Tc = 3840000 Hz.
c) Delay vector is a vector that specifies the propagation delay for each path. In this
project, we assume the delays for 2 paths are 0 second and 2e-6 second and the delays
for 3 paths are 0 second, 2e-6 second and 3e-6 second.
d) Gain vector is a vector that specifies the gain for each path. The gains for 2
paths are 0 dB and -3 dB. The gains for 3 paths are 0 dB, -3 dB and 1 dB.
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e) Normalize gain vector to 0 dB overall gain box. Checking this box causes the
block to scale the Gain vector parameter so that the channel's effective gain (considering
all paths) is 0 decibels.
3.2.2.2 Performance Analysis for Phase 2
Same procedures are used to do the performance analysis for phase 2 as they are
done in phase 1. Performance analysis for this system is based on the following
conditions:
1. BER versus SNR in AWGN and multipath Rayleigh fading channel with Doppler
shift (60kmph, 90kmph and 120kmph) for QPSK modulation technique.
2. BER versus SNR in AWGN and multipath Rayleigh fading channel with Doppler
shift (60kmph, 90kmph and 120kmph) for 16-QAM modulation scheme.
In summary, there are six procedures to be based on for simulation in phase 1 and
phase 2 as they are shown as follows:
1. Bit Error Rate (BER) versus Signal-to-Noise ratio (SNR) in AWGN channel for
QPSK modulation technique.
2. BER versus SNR in AWGN channel for 16-QAM modulation scheme.
3. BER versus SNR in AWGN and multipath Rayleigh fading channel with Doppler
shift (60kmph, 90kmph and 120kmph) for QPSK modulation technique.
4. BER versus SNR in AWGN and multipath Rayleigh fading channel with Doppler
shift (60kmph, 90kmph and 120kmph) for 16-QAM modulation scheme.
5. BER versus SNR to compare between AWGN channel and multipath Raleigh
fading channel for different number of user for QPSK modulation technique.
6. BER versus SNR to compare between AWGN channel and multipath Raleigh
fading channel for different number of user for 16-QAM modulation technique.
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3.3 Simulation Using M file
Another method is simulation using M-files. A script can be written in MATLAB
editor or another text editor to create a file containing the same statements that can be
typed at the MATLAB command line. The file is saved under a name that ends in .m.
The MATLAB language used in m file is a high-level matrix/array language with control
flow statements, functions, data structures, input/output, and object-oriented
programming features. It allows both simple and complicated programs to simulate all
real-time situations.
3.3.1 Generation of Spreading Code
In CDMA, the choice of code sequence is very important in respect to multiuser and
multipath interference encountered by the signal in the channel. To combat these
interferences, the code has to have the following properties:
1. Each code sequence generated from a set of code-generation functions must be
periodic with a constant length.
2. Each code sequence generated from a set of code-generation functions must be
easy to distinguish from its shifted code.
3. Each code sequence generated from a set of code-generation functions must be
easy to distinguish from other code sequences.
The first and second requirements are important with respect to the multipath
propagation effects that occur in mobile outdoor and indoor radio environments.
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However, the third requirement is important with respect to the multiple access
capability of communication systems. Thus, to ensure a distinction level of codes for
requirements 1 and 2, an autocorrelation function and a cross-