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Vietnamese German University
Faculty of Electrical Engineering and Information Technology
Frankfurt University of Applied Sciences
Faculty Computer Science and Engineering
Project Report
Design of a Photovoltaic Power System Using Boost
Converter for DC Applications
Student:
Nguyen Phan Trung Hieu 1067880
Supervisor:
Prof. Dr. Hartmut Hinz
Table of Contents
1. Introduction ................................................................................................................... 1
2. Principle of Operation ................................................................................................... 2
3. Hardware Design ........................................................................................................... 3
3.1. Data acquisition module ......................................................................................... 3
3.1.1. Current measurement ....................................................................................... 4
3.1.2. Voltage measurement ...................................................................................... 6
3.2. Boost Converter ...................................................................................................... 8
3.2.1. Theoretical analysis ......................................................................................... 8
3.2.2. Boost converter realization ............................................................................ 12
3.2.3. Electrical isolation ......................................................................................... 12
3.3. Controller .............................................................................................................. 13
3.3.1. PWM generator ............................................................................................. 13
3.3.2. Data conversion block ................................................................................... 14
4. Photovoltaic module .................................................................................................... 15
5. Proposal for a solar simulator ...................................................................................... 17
5.1. Requirements ........................................................................................................ 17
5.2. Mechanism of mounting angle adjustment ........................................................... 17
5.3. Light source .......................................................................................................... 18
6. References ................................................................................................................... 19
1
1. Introduction
Output power of a photovoltaic (PV) panel does not stay at a fix level, rather vary greatly as
the weather changes moment by moment [1]. Therefore, it is impossible to harness generated
power efficiently if a fix load is directly connected to a PV panel. In addition, output voltage
of PV panel or array of PV panels usually differs from specified operating voltage of DC
loads.
A DC-DC converter serves as a mediate impedance matching device is a well-known
solution for these two problems of photovoltaic power system. Impedance of loads are
relatively constant compared to output impedance of PV panels, which depend dynamically
on many parameters [2]. This suggests that the DC-DC converter of a suitable topology must
also be manipulated dynamically, usually by a PWM signal that controls the conversion
factor, in order to maintain a good matching so that the PV panels always operate at
maximum power-point (MPP).
The aims of this project are to design and to implement a photovoltaic power system that
has the capability of tracking maximum power-point (MPPT) in various testing conditions.
2
2. Principle of Operation
In contrast to the complex behavior of photovoltaic processes, the proposed controlling
method is relatively simple. The block diagram of figure 2.1 is a demonstration for operation
of the whole system.
Figure 2.1 Functional block diagram of the system
Source: drawn by the author
The DC-DC boost converter (Section 3.2) is chosen as impedance matching device for the
fact that output voltage of the PV panel is usually lower than operating voltage levels of DC
loads. The controller (Section 3.3) manipulates the conversion ratio of the boost converter
with the help of PWM generator module (Section 3.3.1). The data acquisition module
(Section 3.1) measures output current and output voltage of the PV panel. The controller
multiplies measured values to compute output power.
In each cycle, the controller adjusts duty cycle of PWM signal in one direction. Measured
values of output current and output voltage are then multiplied to get the value of output
power. The computed value is compared with that of previous cycle. If there is an increase
in output power, the duty cycle is then adjusted in the same direction. Otherwise the
controller make adjustment in the opposite direction.
3
3. Hardware Design
The PV power system designed to be functionality-oriented consists of three separate
modules: data acquisition, controller and boost converter. Some changes in design with
respect to the project proposal are made due to better understandings of the system. The
most important change is to implement electrical isolation in order to guarantee that high
power noises from boost converter does not corrupt the operation of sensitive components
of the controller.
3.1. Data acquisition module
This module performs both voltage measurement and current measurement with the help of
high-accuracy components. The transduced values in form of analog voltages are fed
directly to the controlling module where the digitization takes place.
The module has a separate power supply (9V battery) in order to prevent shutdown in case
the output voltage of the PV drops below 4.5V (which is the lowest high-side supply voltage
of the isolation amplifier [3]). A charging circuit could be easily added if there would be a
requirement of direct power supply from PV panel for better evaluation of efficiency.
Figure 3.1 Layout of the data acquisition module
Source: designed by the author
4
3.1.1. Current measurement
ACS722LLCTR-10AU from Allegro Microsystems is chosen for the implementation of
current measurement function [4]. The current IPV through the main conductor of the IC is
measured base on Hall effect that maintains a good isolation between high-power noisy
signal at the high-side and low-noise low-power signal of sensitive components at the low-
side. The 0.65m primary conductor resistance guarantees very low heating loss [4].
On the other hand, this current sensing method leads to lower accuracy with respect to
current shunt measurement. The specified maximum total output error of ACS722LLCTR-
10AU is 3% [4]. A error model is proposed and discussed later that suggests an empirical
method to eliminate some sources of error in order to achieve a higher accuracy.
Specifications:
Symbol Parameter Value Unit Note
Measuring range 0 10 A
S Sensitivity 264 mV/A
BW Bandwidth 20 kHz
UCC Supply voltage 3 V
Zero-current output voltage 0.3 V 0.1UCC
es Sensitivity error 2 %
uos Offset voltage 15 mV
uo Total output error 3 % without error model
Error model
Figure 4.2 describes three sources of error: Sensitivity error, supply voltage error and offset
voltage. The supply voltage is regulated at 3V by the precision shunt voltage reference IC
LM4040A30 with a tiny error of 0.1% [5] so that UCC is neglected in the error model. The
two remaining error sources are dominant contributors to total output error.
= + 0.1 + ( + )
5
Where:
uo is the output voltage
uos is the offset voltage
S is the sensitivity
es is the sensitivity error
UCC is the supply voltage (UCC = 3V0.1%)
Figure 3.3 Error model of the current measurement
From this model, higher accuracy of current measurement is achieved if the values of uos
and es could be measured using precision equipments. The following procedure should be
performed to determine uos and es :
Set IP = 0A then measure uo, uos could be determined using this formular:
= 0.3
Set IP = 1A then measure uo, es could be determined by:
= 0.3
1 264
Using this error model the resolving formula for the value of IP is derived:
= 0.3
264 +
6
3.1.2. Voltage measurement
Realization of voltage measurement function is based on the isolation fully-differential
amplifier AMC1200 which has a fix precision gain of 8 with maximum gain error of 0.5%
[3]. The output voltage of PV panel is scaled down by a factor of GV using a simple voltage
divider:
= 1 + 2
2=
120 + 1
1= 121
Due to tolerance of the resistors GV must have a small error of eGV. Additionally, a small
offset of output voltage also contributes to total output error at the low-side.
The bandwidth of high-side signal is limited down to about 4kHz by using a passive low-
pass filter:
= 1
2=
1
2(1//2)=
1
2 1 120
121 47= 3.414
The measuring range is designed to be from 0V to 30V. However, if a higher input voltage
is desired, the scale-down fator could be increased easily by replacements of RGV1 and RGV2.
Specifications:
Symbol Parameters Value Unit Note
Measuring range 0 30 V
GV Scale-down factor 121 adjustable
G Gain of isolated amplifier 8 fixed
eG Gain error 0.5 % maximum
eGV Scale-down error 1 %
BW Bandwidth 4 kHz
Error model
Another error model is proposed (Figure 4.3) in order to eliminate dominant error sources.
This model neglect the very small gain error of the amplifier. The following formula of
output voltage is derived from the model:
7
= 8 [
(121 + )+ ]
Where:
uo is the low-side output voltage
UPV is the output voltage of PV panel
GV is the scale-down factor
uos is the high-side input offset voltage
Figure 3.3 Error model of the voltage measurement
Procedure of dominant error sources determination:
Set UPV = 0V then measure the value of uo, uos is computed using:
= 8
Set UPV = 10V then measure uo, the value of eGV could be determined using:
= 10
8
121
With the help of this error model the voltage UPV could be resolve with higher accuracy
using:
= (121 + ) (8
)
8
3.2. Boost Converter
3.2.1. Theoretical analysis
The implementation of a non-isolated boost converter is shown in figure 3.2. The switch is
realized using a high-power MOSFET and a free-wheeling Schottky diode, which introduces
additional losses into the circuit beside heat loss of the inductor. These losses in most cases
deviate the operation of a practical boost converter from that of a ideal one. Therefore, non-
idealities are considered in this analysis in order to work out a more precise behavior of a
boost converter.
Figure 3.4 Schematic of the boost converter
Source: drawn by the author
The practical inductor, which is the energy-storage element of the converter, is modeled
with a small resistance rL in series with an ideal inductor L (figure 3.3). The MOSFET is
modeled with a resistance ron in the on-state and an open circuit in the off-state (figure 3.4).
The free-wheeling Schottky diode is modeled with a ideal voltage source in series with a
resistance in the off-state and an open circuit in the on-state (figure 3.3).
Applying the small-ripple approximation method [6], which treats approximately the
inductor voltage as well as the capacitor current as DC values, the operation of a boost
converter in steady-state with consideration of those losses can be analyzed as follows:
9
Figure 3.5 Boost converter in on-state
Source: drawn by the author
Figure 3.6 Boost converter in off-state
Source: drawn by the author
In the on-state, the MOSFET is turned on and behaves as an ideal resistance ron while the
free-wheeling diode becomes a open circuit. Applying Kirchhoffs voltage law (KVL) and
Kirchhoffs current law (KCL) we have:
: + + + = 0
=
: + = 0
=
In the off-state, the MOSFET is turned off and becomes an open circuit. As the voltage
builds up, the Schottky diode starts to conduct and behaves as a ideal voltage source UD in
series with rD. The following equations can be formulated:
10
: + + + + + = 0
=
: = 0
=
From fundamentals of electrical engineering we know the following relation between
current voltage of an inductor:
=
=
Integration over one switching cycle, says from t = 0 to Ts, yields
= =
0
0
0
In steady-state condition, there is no net change in inductor current. Therefore the right-
hand-side term reduces to zero, leads to
= 0
0
( ) + ( )(1 ) = 0
(1 ) (1 ) (1 ) = 0
The same method is applied for the output capacitor, which yields
( ) + ()(1 ) = 0
(1 ) =
=
(1 )
With this value of iL the previous equation becomes
[
(1 )] [
(1 )
] (1 ) [(1 )(1 )
] (1 ) = 0
(1 ) = [
(1 )+
(1 )
+ (1 )(1 )
+ (1 )]
= [(1 )
+ + (1 ) + (1 )2] [ (1 )]
11
Figure 3.7 Small-ripple approximation for current and voltage waveforms under steady-state operation
Source: drawn by the author
Figure 3.6 Simulation of output voltage and efficiency
Source: executed and visualized by the author
12
3.2.2. Boost converter realization
The main switch is realized using a FCH072N60 N-channel power MOSFET which has a
typical static drain-to-source on resistance of only 66m while maintains a drain-to-source
voltage of upto 600V and a continuous drain current of 33A at 100C [7].
The freewheeling diode is realized using a C3D06065I silicone carbide Schottky diode
which can block a peak reverse voltage of 650V and can maintain a continuous forward
current of 13A [8].
Figure 3.8 Layout of the boost converter
Source: designed by the author
3.2.3. Electrical isolation
As this boost converter is a high-power stage, isolation of power and signal is a crucial task.
The requirement is fulfilled using ISO5500 isolated MOSFET/IGBT driver which is capable
of driving up to 2.5A peak output current [9]. This IC blocks high voltage and prevents high-
power noise from interfering with the controller and from destroying sensitive components.
With this design, the controller can drive high-power MOSFET using low-power logic
signal without any bulky driver circuit.
The ISO5500 gate driver is supply by an external 20V power supply instead of being
supplied directly from the PV panel because ISO5500 has an undervoltage lockout function
13
which turns off its operation when supply voltage drops below 12V [9]. Moreover this
design has the flexibility to connect PV panels in series without violating the maximum
supply voltage of ISO5500 and the maximum gate-to-source voltage of the FCH072N60
power MOSFET.
3.3. Controller
The controller module consists of three blocks with three different functions: PWM
generator, data conversion block and controller block. It is reasonable to locate PWM
generator and analog-to-digital conversion blocks near the controller block in the same
circuit board as they have to communicate with the controller via high-speed serial
interfaces. This design reduces the wiring tasks which are prone to error and also prevent
high-speed digital signals from interfering with analog signal [10].
Figure 3.9 Layout of the controller
Source: designed by the author
3.3.1. PWM generator
The PWM generator is base on the Analog Pulse Width Modulation precision design from
Texas Instruments [11]. Some modifications are made in order to get a full-range of duty
cycle using only positive input voltage. The switching frequency is also limit down to
250kHz.
14
The controller controls the PWM generator by communicating with DAC8830 (a 16-bit
digital-to-analog converter) via a SPI interface. The full-range of duty cycle is mapped to
216 steps that results in high-resolution PWM signal:
= 100%
216= 0.0015%
Specifications:
Symbol Parameter Value Unit Note
D Duty cycle 0 100 %
Resolution 0.0015 %
Ui Input voltage 0 2.5 V
UOH Output high 5 V
UOL Output low 0 V
fs Switching frequency 250 kHz
3.3.2. Data conversion block
ADS131E04 24-bit analog-to-digital converter specified for industrial power applications is
the core of data conversion block [10]. It shares the same serial interface with DAC8830 to
communicate with the controller.
ADS131E04 has four input channels which work independently. Two channels are used for
voltage measurement, the other two are used for current measurement. As only input voltage
and input current from PV panel are monitored, two channels ared reserved for later use.
Specifications:
Symbol Parameter Value Unit Note
Resolution 16, 24 bit programmable
Sampling frequecy 1, 2, 4, 8,
16, 32, 64
kHz programmable
Reference voltage 3 V
Reference error 0.1 %
15
4. Photovoltaic module
Energy for the photovoltaic power system is generated by KC60 PV module from Kyocera
which has the following electrical specifications [12]:
Symbol Parameter Value Unit Note
Pmax Maximum output power 60 W
UOC Open-circuit voltage 21.5 V
ISC Short-circuit current 3.73 A
UMPP MPP voltage 16.9 V
IMPP MPP current 3.55 A
Because of highly ideal test condition of the provided specifications, the actual KC60 PV
panel to be used in this project is tested for real-life behaviors under two conditions as shown
in figure 4.1.
Figure 4.1 Experiment setups (left: testing under halogen lamp, right: testing under direct sunlight)
Source: photographed by the author
In the first experiment (right-hand side picture), a 400-W halogen lamp (available in the
laboratory) is used as light source of the PV panel. In this experiment setup, KC60 panel
only produces a tiny output power (figure 4.2). The result suggests that the proposed halogen
lamp is not suitable for testing of the system in further stages.
16
In the second experiment (left-hand side picture), the PV panel is tested under direct sunlight
(2 p.m, May 22th 2015, high sun, no cloud) and produces a much better output
characteristics (figure 4.3).
Figure 4.2 Output characteristic under halogen lamp
Source: photographed by the author
Figure 4.3 Output characteristics under direct sunlight
Source: photographed by the author
17
5. Proposal for a solar simulator
Experiences from previous projects show that the development of photovoltaic power
systems is slowed down greatly if the testing is dependent entirely on direct sunlight which
cannot be manipulated. Therefore a designed of a solar simulator is proposed, with which
small PV systems could be tested conviniently in laboratory.
5.1. Requirements
The proposed solar simulator should provide enough space to mount two KC60 PV panels
(650x750mm each one). The connection of this two panels, in series or in parallel, should
be managed conviniently with the help of a connection box. The angle of the frame, onto
which the two PV panels are mounted, must be adjustable in order to test the behaviours of
the system under various irradiance angle.
The light source should be able to produce an irradiance of up to 1000W/m2 with a good
spectral match. The light source should also be dismountable so that testing under direct
sunlight could be performed if needed.
5.2. Mechanism of mounting angle adjustment
Figure 5.1 describes how mounting angle of the two PV panels is adjusted.
Figure 5.1 Angle adjustment mechanism
18
AB is the frame on which PV panels are mounted. The frame is fixed at pivot B so that A
can rotate around B. The fix-length arm AS connects pivot A to slider S, which can move
in horizontal direction with the help of a linear actuator.
At the right-most point of the slider S, frame AB is in horizontal direction. Rotation of the
linear actuator brings slider S to the right. As the lenght of AS cannot be changed, point A
also rotates around fixed pivot B that results in a angle of the whole frame with respect to
the horizontal line.
5.3. Light source
The SUNLIKE products from FUTURELED appear to be a promising candidate for the
proposed solar simulator.
Ten modules of standard size SUNLIKE L (300x300mm) could be assembled together to
cover a total size of 600x1500mm, which fits perfectly to the total area of two KC60
panels.
A more detail design cannot be made at the moment due to lack of documentation of the
products.
19
6. References
[1] E. F. Fuchs and M. A. S. Masoum, Power Conversion of Renewable Energy
Systems, New York: Springer, 2012.
[2] T. Markvart and L. Castaer, Practical Handbook of Photovoltaics: Fundamentals
and Applications, Oxford: Elsevier, 2003.
[3] Texas Instruments, AMC1200 Fully Differential Isolation Amplifier, 2012.
[4] Allegro Microsystems, ACS722 High Accuracy, Galvanically Isolated Current
Sensor, 2014.
[5] Texas Instruments, LM4040Axx Precision Micropower Shunt Voltage Reference,
2015.
[6] R. W. Erickson and D. Maksimovi, Fundamentals of Power Electronics, New York:
Kluwer Academic Publishers, 2004.
[7] Fairchild Semiconductors, FCH072N60 N-Channel SuperFET MOSFET, 2014.
[8] Cree, C3D06065I Silicone Carbide Schottky Diode Rev. A, 2012.
[9] Texas Instruments, ISO5500 2.5A Isolated IGBT, MOSFET Gate Driver, 2015.
[10] Texas Instruments, ADS131E04 Analog Front-End for Power Mornitoring, Control
and Protection, 2013.
[11] Texas Instrument: Caldwell, John, TI Precision Designs: Analog Pulse Width
Modulation, 2013.
[12] Kyocera, KC60 High Efficiency Multicrystal Photovoltaic Module.