MAE 4421 – Control of Aerospace & Mechanical Systems
SECTION 7: FREQUENCY‐RESPONSE ANALYSIS
K. Webb MAE 4421
Introduction2
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Introduction
We have seen how to design feedback control systems using the root locus
In this section of the course, we’ll learn how to do the same using the open‐loop frequency response
Objectives: Review frequency‐response fundamentals Relate a system’s frequency response to its transient response
Determine static error constants from the open‐loop frequency response
Determine closed‐loop stability from the open‐loop frequency response
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System Response to a Sinusoidal Input
Consider an ‐order system poles: , , … Real or complex Assume all are distinct
Transfer function is:
⋯(1)
Apply a sinusoidal input to the system
sin
Output is given by
⋯∙ (2)
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System Response to a Sinusoidal Input
Partial fraction expansion of (2) gives
⋯ (3)
Inverse transform of (3) gives the time‐domain output
⋯ cos sin (4)
transient steady state
Two portions of the response: Transient Decaying exponentials or sinusoids – goes to zero in steady state Natural response to initial conditions
Steady state Due to the input – sinusoidal in steady state
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Steady‐State Sinusoidal Response
We are interested in the steady‐state response
cos sin (5)
A trig. identity provides insight into :
cos sin sinwhere
tan
Steady‐state response to a sinusoidal input
sin
is a sinusoid of the same frequency, but, in general different amplitude and phase
sinWhere (6)
and tan
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Steady‐State Sinusoidal Response
sin → sin
Steady‐state sinusoidal response is a scaled andphase‐shifted sinusoid of the same frequency Equal frequency is a property of linear systems
Note the term in the numerator of (3) will affect the residues Residues determine amplitude and phase of the output Output amplitude and phase are frequency‐dependent
sin
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Steady‐State Sinusoidal Response
Gain – the ratio of amplitudes of the output and input of the system
Phase – phase difference between system input and output
Systems will, in general, exhibit frequency‐dependent gain and phase
We’d like to be able to determine these functions of frequency The system’s frequency response
Linear Systemsin sin
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A system’s frequency response, or sinusoidal transfer function, describes its gain and phase shift for sinusoidal inputs as a function of frequency.
Frequency Response9
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Frequency Response
System output in the Laplace domain is⋅
Multiplication in the Laplace domain corresponds to convolution in the time domain
∗
Consider an exponential input of the form
where is the complex Laplace variable:
Now the output is
∗
⋅ (1)
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Frequency Response
⋅ (1)
We’re interested in the steady‐state response, so let the upper limit of integration go to infinity
⋅
⋅ (2)
Time‐domain response to an exponential input is the time‐domain input multiplied by the system transfer function
What is this input?(3)
If we let → 0, i.e. let → , then we have
⋅ (4)
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Euler’s Formula
Recall Euler’s formula:
cos sin (5)
From which it follows that
cos (6)
and
sin (7)
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Frequency Response
We’re interested in the sinusoidal steady‐state system response, so let the input be
cos 2
A sum of complex exponentials in the form of (3) We’ve let → in the first term and → in the second
(8)
According to (4) the output in response to (8) will be
⋅ ⋅ (9)
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Frequency Response
⋅ ⋅ (9)
is a complex function of frequency Evaluates to a complex number at each value of Has both magnitude and phase Can be expressed in polar form as
(10)
whereand ∠
It follows that
(11)
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Frequency Response
Using (11), the output given by (9) becomes
(12)
(13)
where, again
and ∠ (14)
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Frequency response Function –
is the system’s frequency response function Transfer function, where →
| → (15)
A complex‐valued function of frequency
at each is the gain at that frequency Ratio of output amplitude to input amplitude
∠ at each is the phase at that frequency Phase shift between input and output sinusoids
Another representation of system behavior Along with state‐space model, impulse/step responses, transfer
function, etc. Typically represented graphically
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Plotting the Frequency Response Function
is a complex‐valued function of frequency Has both magnitude and phase Plot gain and phase separately
Frequency response plots formatted as Bode plots Two sets of axes: gain on top, phase below Identical, logarithmic frequency axes Gain axis is logarithmic – either explicitly or as units of decibels (dB)
Phase axis is linear with units of degrees
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Bode Plots
Logarithmic frequency axes
Units of magnitude are dB Magnitude
plot on top
Phase plot below
Units of phase are degrees
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Interpreting Bode Plots
Bode plots tell you the gain and phase shift at all frequencies: choose a frequency, read gain and phase values from the plot
For a 10KHz sinusoidal input, the gain is 0dB (1) and the phase shift is 0°.
For a 10MHz sinusoidal input, the gain is ‐32dB (0.025), and the phase shift is ‐176°.
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Interpreting Bode Plots
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Decibels ‐ dB
Frequency response gain most often expressed and plotted with units of decibels (dB) A logarithmic scale Provides detail of very large and very small values on the same plot
Commonly used for ratios of powers or amplitudes
Conversion from a linear scale to dB:
20 ⋅ log
Conversion from dB to a linear scale:
10
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Decibels – dB
Multiplying two gain values corresponds to adding their values in dB E.g., the overall gain of cascaded systems
⋅
Negative dB values corresponds to sub‐unity gain Positive dB values are gains greater than one
dB Linear
60 1000
40 100
20 10
0 1
dB Linear
6 2
‐3 1/√2 0.707‐6 0.5
‐20 0.1
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Value of Logarithmic Axes ‐ dB
Gain axis is linear in dB A logarithmic scale Allows for displaying detail at very large and very small levels on the same plot
Gain plotted in dB Two resonant peaks
clearly visible
Linear gain scale Smaller peak has
disappeared
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Value of Logarithmic Axes ‐ dB
Frequency axis is logarithmic Allows for displaying detail at very low and very high frequencies on the
same plot
Log frequency axis Can resolve
frequency of both resonant peaks
Linear frequency axis Lower resonant
frequency is unclear
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Gain Response – Terminology
Corner frequency, cut off frequency, ‐3dB frequency: Frequency at which
gain is 3dB below its low‐frequency value
2
This is the bandwidthof the system
Peaking Any increase in gain
above the low frequency gain
1.45
2 0.23
~5 of peaking
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Frequency‐Response Factors26
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Transfer Function Factors
Numerator and denominator of a transfer function can be factored into first‐ and second‐order terms
⋯ 2 2 ⋯⋯ 2 2 ⋯
Can think of the transfer function as a product of the individual factors
For example, consider the following system
2
Can rewrite as
⋅1
⋅1
2
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Transfer Function Factors
⋅1
⋅1
2
Think of this as three cascaded transfer functions, ,
1 12
or
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Transfer Function Factors
In the Laplace domain, transfer function of a cascade of systems is the product of the individual transfer functions In the time domain, overall impulse response is the convolution of the individual impulse responses
Same holds true in the frequency domain Frequency response of a cascade is the product of the individual frequency responses
Or, the product of individual factors
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Frequency Response Components ‐ Example
Consider the following system
20 201 100
The system’s frequency response function is
20 201 100
As we’ve seen we can consider this a product of individual frequency response factors
20 ⋅ 20 ⋅11 ⋅
1100
Overall response is the composite of the individual responses Product of individual gain responses – sum in dB Sum of individual phase responses
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Frequency Response Components ‐ Example
Gain response
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Frequency Response Components ‐ Example
Phase response
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In this section, we’ll look at a method for sketching, by hand, a straight‐line, asymptotic approximation for a Bode plot.
Bode Plot Construction33
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Bode Plot Construction
We’ve just seen that a system’s frequency response function can be factored into first‐ and second‐order terms Each factor contributes a component to the overall gain and phase responses
Now, we’ll look at a technique for manually sketching a system’s Bode plot In practice, you’ll almost always plot with a computer But, learning to do it by hand provides valuable insight
We’ll look at how to approximate Bode plots for each of the different factors
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Bode Form of the Transfer function
Consider the general transfer function form:⋯ 2 ⋯⋯ 2 ⋯
We first want to put this into Bode form:
1 1 ⋯ 2 1 ⋯
1 1 ⋯ 2 1 ⋯
The corresponding frequency response function, in Bode form, is
1 1 ⋯ 2 1 ⋯
1 1 ⋯ 2 1 ⋯
Putting into Bode form requires putting each of the first‐ and second‐order factors into Bode form
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First‐Order Factors in Bode Form
First‐order frequency‐response factors include:
, ,
For the first factor, , is a positive or negative integer Already in Bode form
For the second two, divide through by , giving
1 and
Here, , the corner frequency associated with that zero or pole, so
1 and
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Second‐Order Factors in Bode Form
Second‐order frequency‐response factors include:
2 and
Again, normalize the coefficient, giving
1 and /
Putting each factor into its Bode form involves factoring out any DC gain component
Lump all of DC gains together into a single gain constant,
⋯ ⋯
⋯ ⋯
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Bode Plot Construction
Frequency response function in Bode form ⋯ ⋯
⋯ ⋯
Product of a constant DC gain factor, , and first‐and second‐order factors
Plot the frequency response of each factor individually, then combine graphically Overall response is the product of individual factors Product of gain responses – sum on a dB scale Sum of phase responses
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Bode Plot Construction
Bode plot construction procedure:1. Put the sinusoidal transfer function into Bode form2. Draw a straight‐line asymptotic approximation for the
gain and phase response of each individual factor3. Graphically add all individual response components
and sketch the result
Next, we’ll look at the straight‐line asymptotic approximations for the Bode plots for each of the transfer function factors
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Bode Plot – Constant Gain Factor40
Constant gain
Constant Phase
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Bode Plot – Poles/Zeros at the Origin41
0: zeros at the origin
0: poles at the origin
Gain: Straight line Slope ⋅ 20 ⋅ 6
0 at 1
Phase: ∠ ⋅ 90°
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Bode Plot – First‐Order Zero42
Single real zero at
Gain: 0 for
20 6 for
Straight‐line asymptotes intersect at , 0
Phase: 0° for 0.1 45° for 90° for 10
° for 0.1 10
1
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Bode Plot – First‐Order Pole43
Single real pole at
Gain: 0 for
20 6 for
Straight‐line asymptotes intersect at , 0
Phase: 0° for 0.1 45° for 90° for 10
° for 0.1 10
1
1
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Bode Plot – Second‐Order Zero44
Complex‐conjugate zeros:
,
Gain: 0 for ≪ 40 12 for ≫ Straight‐line asymptotes intersect at
, 0
‐dependent peaking around
Phase: 0° for ≪ 90° for
180° for ≫ ‐dependent slope through
Sketch as step‐change at for low , 90°/ for high , or in between
21
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Bode Plot – Second‐Order Pole45
12 1
Complex‐conjugate poles:
,
Gain: 0 for ≪ 40 12 for ≫ Straight‐line asymptotes intersect at
, 0
‐dependent peaking around
Phase: 0° for ≪ 90° for
180° for ≫ ‐dependent slope through
Sketch as step‐change at for low , 90°/ for high , or in between
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Bode Plot Construction – Example46
Consider a system with the following transfer function
10 20400
The sinusoidal transfer function:
10 20400
Put it into Bode form
10 ⋅ 20 20 1
⋅ 400 400 1
0.5 20 1
⋅ 400 1
Represent as a product of factors
0.5 ⋅ 20 1 ⋅1⋅
1
400 1
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Bode Plot Construction – Example
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Bode Plot Construction – Example
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Polar Frequency Response Plots49
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Polar Frequency Response Plots
is a complex function of frequency Typically plot as Bode plots Magnitude and phase plotted separately Aids visualization of system behavior
A real and an imaginary part at each value of A point in the complex plane at each frequency Defines a curve in the complex plane A polar plot Parametrized by frequency – not as easy to distinguish frequency as on a Bode plot
Polar plots are not terribly useful as a means of displaying a frequency response However, an important concept later, when we introduce the Nyquist stability criterion
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Polar Frequency Response Plots
Identical frequency responses plotted two ways: Bode plot and polar plot
Note uneven frequency spacing along polar plot curve Dependent on frequency rates of change of gain and phase
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Relationship between Frequency Response and Transient Response
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Transient/Frequency Response Relationship
We have seen relationships – some exact, some approximate – between closed‐loop pole locations and closed‐loop transient response
Also have relationships between closed‐loop frequency response and closed‐loop transient responses
Applicable to second‐order systems:
2
Also applicable to higher‐order systems that are reasonably approximated as second‐order Systems with a pair of dominant second‐order poles
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Transient/Frequency Response Relationship
Damping ratio vs. overshoot vs. peaking
Natural frequency vs. risetime vs. bandwidth
Qualitative 2nd‐order time/freq. response/pole relationships
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Frequency Response Peaking
For systems with 0.707, the gain response will exhibit peaking
Can relate peak magnitudeto the damping ratio
12 1
Relative to low‐frequency gain
And the peak frequency to the damping ratio and natural frequency
1 2
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Transient/Frequency Response Relationship
Can also relate a system’s bandwidth (i.e., ‐3dB frequency, ) to the speed of its step response
Bandwidth as a function of and
1 2 4 4 2
Bandwidth as a function of 1% settling time and
4.61 2 4 4 2
Bandwidth as a function of peak time and
11 2 4 4 2
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Steady‐State Error from Bode Plots57
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Static Error Constants
For unity‐feedback systems, open‐loop transfer function gives static error constants Use static error constants to calculate steady‐state error
lim→
lim→
lim→
We can also determine static error constants from a system’s open‐loop Bode plot
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Static Error Constant – Type 0
For a type 0 system
→
At low frequency, i.e. below any open‐loop poles or zeros
Read directly from the open‐loop Bode plot Low‐frequency gain
100 303 200
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Static Error Constant – Type 1
For a type 1 systemlim→
At low frequencies, i.e. below any other open‐loop poles or zeros
and
A straight line with a slope of / Evaluating this low‐frequency asymptote at yields the velocity constant,
On the Bode plot, extend the low‐frequency asymptote to Gain of this line at 1 is
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Static Error Constant – Type 1
85 0.1 5010 125
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Static Error Constant – Type 2
For a type 2 systemlim→
At low frequencies, i.e. below any other open‐loop poles or zeros
and
A straight line with a slope of / Evaluating this low‐frequency asymptote at yields the acceleration constant,
On the Bode plot, extend the low‐frequency asymptote to Gain of this line at 1 is
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Static Error Constant – Type 2
1600 0.1 5100
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Nyquist Stability Criterion64
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Stability
Consider the following system
We already have a couple of tools for assessing stability as a function of loop gain, Routh Hurwitz Root locus
Root locus: Stable for some values of Unstable for others
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Stability
In this case gain is stable below some value
Other systems may be stable for gain abovesome value
Marginal stability point: Closed‐loop poles on the imaginary axis at
For gain
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Open‐Loop Frequency Response & Stability
Marginal stability point occurs when closed‐loop poles are on the imaginary axis Angle criterion satisfied at
1 and ∠ 180°
Note that
is the open‐loop frequency response Marginal stability occurs when:
Open‐loop gain is: Open‐loop phase is:
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Stability from Bode Plots
Here, stable for smaller gain values 0 when∠ 180°
Often, stable for larger gain values 0 when∠ 180°
Root locus provides this information Bode plot does not
Varying simply shifts gain response up or down
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Open‐Loop Frequency Response & Stability
A method does exist for determining stability from the open‐loop frequency response:
Nyquist stability criterion Graphical technique Uses open‐loop frequency response Determine system stability Determine gain ranges for stability
Before introducing the Nyquist criterion, we must first introduce the concept of complex functional mapping
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Complex Functional Mapping
Consider a complex function⋯⋯
Takes one complex value, , and yields a second complex value, In other words, it maps to
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Mapping of Contours
provides a mapping of individual points in the s‐plane to corresponding points in the F‐plane
Can also map all points around a contour in the s‐plane to another contour in the F‐plane
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Mapping of Contours
Recall how we approached the application of the angle criterion Vector approach to the evaluation of a transfer function at a particular point in the s‐plane
∏ ∏
∠ Σ∠ Σ∠
Can take the same approach to evaluating complex functions around contours in the s‐plane
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Mapping Contours – Example 1
Map contour by in a clockwise direction Contour does not enclose the zero
Here, , so and ∠ ∠
As is evaluated around , ∠ never exceeds 0° or 180° does the same:
Does not rotate through a full 360° Contour does not encircle the origin
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Mapping Contours – Example 2
Map contour by in a clockwise direction Contour does not enclose the pole
Here, 1/ , so 1/ and ∠ ∠
∠ oscillates over some range well within 0° and 180° rotates through the negative of the same range Contour does not encircle the origin
1
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Mapping Contours – Example 3
Now, contour encloses a single zero
, so and ∠ ∠
rotates through a full 360° in a clockwise direction does the same:
Contour encircles the origin in a clockwise direction
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Mapping Contours – Example 4
Now, contour encloses a single pole
1/ , so 1/ and ∠ ∠
rotates through a full 360° in a clockwise direction rotates in the opposite direction Contour encircles the origin in a CCW direction
1
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Mapping Contours – Example 5
Now, contour encloses two poles
, so and ∠ ∠ ∠
and each rotate through a full 360° in a clockwise direction rotates in the opposite direction Contour encircles the origin twice in a CCW direction
1
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Mapping Contours – Example 6
∠ and∠ rotate through 360° in a CW direction Their contributions rotate in opposite directions ∠ does not rotate through a full 360° Contour does not encircle the origin
Now, contour encloses one pole and one zero
, so and ∠ ∠ ∠
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Complex Functional Mapping of Contours
Some observations regarding complex mapping of contour in a CW direction to contour : If does not enclose any poles or zeros, does not encircle the origin
If encloses a single pole, will encircle the origin once in a CCW direction
If encloses two poles, will make two CCW encirclements of the origin
If encloses a pole and a zero, will not encircle the origin
Next, we’ll use these observations to help derive the Nyquist stability criterion
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Nyquist Stability Criterion
Our goal is to assess closed‐loop stability Determine if there are any closed‐loop poles in the RHP
Consider a generic feedback system:
Closed‐loop transfer function
1
Closed‐loop poles are roots (zeros) of the closed‐loop characteristic polynomial:
1
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Nyquist Stability Criterion
Can represent the individual transfer functions as
and
The closed‐loop polynomial becomes
1 1
From this, we can see that: The poles of 1 are the poles of , the open‐loop poles
The zeros of 1 are the poles of , the closed‐loop poles
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Nyquist Stability Criterion
To determine stability, look for RHP closed‐loop poles Evaluate 1 CW around a contour that encircles the entire right half‐plane Evaluate 1 along entire
‐axis Encircle the entire RHP with an infinite‐radius arc
If 1 has one RHP pole, resulting contour will encircle the origin once CCW
If 1 has one RHP zero, resulting contour will encircle the origin once CW
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Nyquist Stability Criterion
Total number of CW encirclements of the origin, , by the resulting contour will be
# of RHP poles of 1 # of RHP zeros of 1
Want to detect RHP poles of , zeros of 1 , so
# of closed‐loop RHP poles
# of open‐loop RHP poles
# of CW encirclements of the origin
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Nyquist Stability Criterion
Basis for detecting closed‐loop RHP polesMap contour encircling the entire RHP through closed‐loop characteristic polynomial
Count number of CW encirclements of the origin by resulting contour
Calculate the number of closed‐loop RHP poles:
Need to know: Closed‐loop characteristic polynomial Number of RHP poles of closed‐loop characteristic polynomial
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Nyquist Stability Criterion
Open‐loop transfer function Easy to use for mapping – we know poles and zeros
Resulting contour shifts left by 1 – that’s all
Now, count encirclements of the point
Instead, map through
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Nyquist Stability Criterion
Nyquist stability criterion If a contour that encloses the entire RHP is mapped through the open‐loop transfer function, , then the number of closed‐loop RHP poles, , is given by
where
# of CW encirclements of # of open‐loop RHP poles
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Nyquist Stability Criterion
Want to detect net clockwise encirclements# CW encirclements ‐ # CCW encirclements
Draw a line from in any
direction Count number of times contour crosses the line in each direction
2
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Nyquist Diagram
The contour that results from mapping the perimeter of the entire RHP is a Nyquist diagram
Consider four segments of the contour:
①②
③
④
1) Along positive ‐axis, we’re evaluating ) Open‐loop frequency response
2) Here, → Maps to zero for any physical system
3) Here, evaluating ) Complex conjugate of segment ① Mirror ① about the real axis
4) The origin Sometimes a special case – more later
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Nyquist Criterion – Example 1
Apply the Nyquist criterion to determine stability for the following system
First evaluate along segment ①, ‐axis This is the frequency response
Read values off of the Bode plot
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Nyquist Criterion – Example 1
Segment ① is a polar plot of the frequency response
All of segment ②, arc at , maps to the origin
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Nyquist Criterion – Example 1
Segment ③ is the complex conjugate of segment ①Mirror about the real axis
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Nyquist Criterion – Example 1
Count CW encirclements of Draw a line from 1 in any direction
Here, Closed‐loop RHP poles given by:
No open‐loop RHP poles, so
Two RHP poles, so system is unstable
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Nyquist Criterion – Example 2
This system is open‐loop stable Stable for low enough Nyquist plot will not encircle
Three poles and no zeros Unstable for above some value Nyquist plot will encircle
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Nyquist Criterion – Example 2
For , , and the system is stable Modifying simply scales the magnitude of the Nyquist plot
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Nyquist Criterion – Example 2
Here, the Nyquist plot crosses the negative real axis at
As gain increases real‐axis crossing moves to the left
Increasing by 2x or more results in two encirclements of
Unstable for 60 More later …
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Nyquist Diagram – Poles at the Origin
We evaluate the open‐loop transfer function along a contour including the ‐axis
is undefined at the pole Must detour around the pole
Consider the common case of a pole at the origin
④
This is the special case for segment ④
12
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④
97
Nyquist Diagram – Poles at the Origin
Segment ④ contour: for 0° 90° Evaluate around segment ④ as
12
Magnitude:1
212
As → 0lim→
∞
Maps to an arc at
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④
98
Nyquist Diagram – Poles at the Origin
Segment ④ traversed in a CCW direction varies from
Phase of the resulting contour:
∠
Negative because it is angle from a pole
Extra phase from additional pole
maps segment ④ to: An arc at Rotating CW from 0° to 90°
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Nyquist Criterion – Example 3
Apply the Nyquist criterion to determine stability for the following system
Use Bode plot to map segment ① Infinite DC gain Starts at at for
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Nyquist Criterion – Example 3
Segment ① starts at at Heads to the origin at All of segment ②, arc at , maps to the origin
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Nyquist Criterion – Example 3
Segment ③ is the complex conjugate of segment ①Mirror about the real axis
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Nyquist Criterion – Example 3
Segment 4 maps to a CW arc at CW, so it does not encircle Can’t draw to scale
Here, No open‐loop RHP poles, so
No RHP poles, so system is stable
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Stability Margins103
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Stability Margins
Recall a previous example
According to the Nyquist plot, the system is stable How stable?
Two stability metrics Both are measures of how close the Nyquist plot is to encircling the point 1
Gain margin and phase margin
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Crossover Frequencies
Two important frequencies when assessing stability:
Gain crossover frequency The frequency at which the open‐loop gain crosses
Phase crossover frequency The frequency at which the open‐loop phase crosses
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Gain Margin
An open‐loop‐stable system will be closed‐loop stable as long as its gain is less than unity at the phase crossover frequency
Gain margin, GM The change in open‐loop gain at the phase crossover frequency required to make the closed‐loop system unstable
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Phase Margin
An open‐loop‐stable system will be closed‐loop stable as long as its phase has not fallen below at the gain crossover frequency
Phase margin, PM The change in open‐loop phase at the gain crossover frequency required to make the closed‐loop system unstable
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Gain and Phase Margins from Bode Plots
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Phase Margin and Damping Ratio,
PM can be expressed as a function of damping ratio, , as
tan
For 65° or so, we can approximate:
100 or
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Frequency Response Analysis in MATLAB110
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bode.m
[mag,phase] = bode(sys,w)
sys: system model – state‐space, transfer function, or other w: optional frequency vector – in rad/sec mag: system gain response vector phase: system phase response vector – in degrees
If no outputs are specified, bode response is automatically plotted – preferable to plot yourself
Frequency vector input is optional If not specified, MATLAB will generate automatically
May need to do: squeeze(mag) and squeeze(phase)to eliminate singleton dimensions of output matrices
K. Webb MAE 4421
112
nyquist.m
nyquist(sys,w) sys: system model – state‐space, transfer function, or other w: optional frequency vector – in rad/sec
MATLAB generates a Nyquist plot automatically Can also specify outputs, if desired:
[Re,Im] = nyquist(sys,w)
Plot is not be generated in this case
K. Webb MAE 4421
113
margin.m
[GM,PM,wgm,wpm] = margin(sys)
sys: system model – state‐space, transfer function, or other GM: gain margin PM: phase margin – in degrees wgm: frequency at which GM is measured, the phase crossover frequency – in rad/sec
wpm: frequency at which PM is measured, the gain crossover frequency
If no outputs are specified, a Bode plot with GM and PM indicated is automatically generated