November 2006
Slide 1
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Project: IEEE P802.15 Working Group for Wireless Personal Area NProject: IEEE P802.15 Working Group for Wireless Personal Area Networks (etworks (WPANsWPANs))
Submission Title: [RF impairment models for 60GHz-band SYS/PHY simulation]Date Submitted: [November, 2006]Source: [Chang-Soon Choi, Yozo Shoji, Hiroshi Harada, Ryuhei Funada, Shuzo Kato, Kenichi Maruhashi, Ichihiko Toyoda, and Kazuaki Takahashi] Company [NICT, NEC, NTT, and Panasonic]Address [3-4, Hikarino-Oka, Yokosuka, Kanagawa, 239-0847, Japan]Voice:[+81.46.847.5096], FAX: [+81.46.847.5079], E-Mail:[[email protected], [email protected], [email protected], [email protected] , [email protected], [email protected], [email protected], [email protected]]Re: []
Abstract: [This contribution describes RF impairment models for 60GHz-band SYS/PHY simulation.]
Purpose: [Contribution to mmW TG3c meeting.]Notice: This document has been prepared to assist the IEEE P802.15. It is offered as a basis for discussion and is not binding on the contributing individual(s) or organization(s). The material in this document is subject to change in form and content after further study. The contributor(s) reserve(s) the right to add, amend or withdraw material contained herein.Release: The contributor acknowledge and accept that this contribution becomes the property of IEEE and may be made publicly available by P802.15.
November 2006
Slide 2
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
RF impairment modelsfor 60GHz-band SYS/PHY simulation
Chang-Soon Choi1, Yozo Shoji1, Hiroshi Harada1, Ryuhei Funada1, Shuzo Kato1, Kenichi Maruhashi2, Ichihiko Toyoda3,and Kazuaki Takahashi4
1 NiCT, 2 NEC, 3 NTT and 4 Panasonic, Japan
November 2006
Slide 3
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
090
090
PLL
Osc.
VGA
LNA
PA
I/Q mod
I/Q demod
BPF
T/R switch
PA driver
BPF
BPF
BPF VGA
VGA
ADC
ADC
DAC
DAC
Background: RF impairments to be considered
Nonlinear PA transfer curvesfor amplitude (AM-AM) and phase (AM-PM)
Phase-noise from VCO/PLL
I/Q mismatch
ADC/DACquantization
noise
November 2006
Slide 4
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Effects of HPA nonlinearity
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Impact of HPA on constellation After PABefore PA
-35 -30 -25 -20 -15 -10 -5 0 5-10
-5
0
5
10
15
-15
-10
-5
0
5
10
15
20
Input power [dBm]
Out
put p
ower
[dB
m]
Output phase change [degree]
AM-AM effect
AM-PM effect
Input power
NonlinearHPA
- HPA nonlinear relationshipbetweenoutput power and input power(AM-AM effect) andoutput phase and input power(AM-PM effect)
- Ghorbani model was suggestedin Melbourne meeting
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Transmitted 16QAM signal
- GaAs pHEMT 60GHz power amplifier- Refer to 15-06-0396-01-003c
November 2006
Slide 5
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Power amplifier model for TG3c:Modified Rapp model
pp
sat
AMAM
VGx
GxyF21
2
1
)(
⎟⎟
⎠
⎞
⎜⎜
⎝
⎛⎟⎟⎠
⎞⎜⎜⎝
⎛+
=−
- Rapp model has been used for IEEE standardization (ex. 802.11a, 11n)- Rapp model is convenient for setting parameters, Saturation (Vsat) and Gain (G)- Suggested the equation to express AM-PM effect = Modified Rapp model
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.450
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
2
Input signal voltage [V]
Out
put s
igna
l vol
tage
[V]
AM-AM effect
Modified Rapp modelMeasured (NEC)
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45-0.3
-0.25
-0.2
-0.15
-0.1
-0.05
0
0.05
Input signal voltage [V]
Out
put s
igna
l pha
se [r
ad]
AM-PM effect
Modified Rapp modelMeasured (NEC)
⎟⎟⎠
⎞⎜⎜⎝
⎛⎟⎠⎞
⎜⎝⎛+
=− q
q
PMAM
Bx
AxF1
)(θ
AM-AM AM-PM
November 2006
Slide 6
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
What parameter should we use for PA simulation?Output BACKOFF
- Output backoff affects system performance and adjacent channel power ratio- higher backoff, higher linearity
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Received signalAfter HPABefore HPA
-2 -1.5 -1 -0.5 0 0.5 1 1.5 2
-100
-90
-80
-70
-60
-50
-40
-30
-20
Frequency [GHz]
Out
put p
ower
[dB
m]
Input signal to PAOutput signal from PA
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Received signal
After HPABefore HPA
-2 -1.5 -1 -0.5 0 0.5 1 1.5 2
-100
-90
-80
-70
-60
-50
-40
-30
-20
Frequency [GHz]
Out
put p
ower
[dB
m]
Input signal to PAOutput signal from PA
-30 -25 -20 -15 -10 -5 0 5
5
10
15
-10
0
10
20
30
Input power [dBm]
Out
put p
ower
[dB
m]
Output phase [degree]
A: OBO = 2dB
B: OBO = 5dB
(A)
(B)
Modified Rapp model
AM-AM AM-PM
November 2006
Slide 7
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Effect of output BACKOFF onBER and power efficiency
- Higher backoff, higher linearity, but lower power efficiency (trade-off)- Backoff is critical parameter to decide power consumption and nonlinearity- Let’s use this parameter with modified Rapp model for PA simulation
5 10 15 20
10-6
10-5
10-4
10-3
10-2
10-1
Without PA5dB OBO
OBO: output backoff
4dB OBO3dB OBO2dB OBO1dB OBO
- Modified Rapp model- 2Gbps 16QAM,- Roll-off factor (r) = 0.5- No FEC, AWGN
Eb/N0
BER
Fig.1: Impact of output backoff on 16QAM transmission Fig.2: Ideal power efficiency vs. output backoff
0 2 4 6 8 100
5
10
15
20
25
30
35
40
45
50
Output backoff [dB]
Pow
er e
ffici
ency
[%]
Theory
AssumingClass A operation
November 2006
Slide 8
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Effects of phase-noise
Phasenoise
Phase-noise
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Scatter plot
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Received signal After phase-noiseBefore phase-noise
105
106
107
108
109
1010
-160
-150
-140
-130
-120
-110
-100
-90
-80
Frequency offset [Hz]
Pha
se-n
oise
spe
ctra
l den
sity
[dB
c/H
z]
Generated phase-noiseInterpolated data
- Interpolation data between adapted phase-noise data from reference [1](0.13um CMOS-based 60GHz VCO)
- Assuming 1MHz PLL loop bandwidth- Phase-noise significantlyaffects system performance
November 2006
Slide 9
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Phase-noise model for TG3c:PLL/VCO and its model
Ignoringflicker noise andRef. oscillator noise
Log (freq)
Phas
e-no
ise
spec
tral d
ensi
ty [d
Bc/
Hz]
2
1f
Open loop VCO
Fig.1: Phase-noise characteristics for VCO and PLL
105 106 107 108 109 1010-130
-120
-110
-100
-90
-80
-70
phase-noise modelpole frequencyzero frequency
Fig.2: Proposed phase-noise model for TG3c
])/(1[])/(1[)0()( 2
2
p
z
ffffPSDfPSD
++
=
PSD(0) = - 87 dBc/Hzpole frequency fp = 1MHzzero frequency fz = 100MHz
Frequency [Hz]Ph
ase-
nois
e [d
Bc/
Hz]
- Proposed model is well expressing this PLL phase-noise characteristic.
- PLL effectively suppresses low frequency noise of VCO,making it possible to transmit phase-modulated data signal.
PLL loop bandwidth loopf
PLL output
Reduction of VCO noise
Noise
November 2006
Slide 10
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Effect of phase-noise parameters on performance
5 10 15 2010-7
10-6
10-5
10-4
10-3
10-2
])/(1[])/(1[)0()( 2
2
p
z
ffffPSDfPSD
++
=- 1 pole, 1 zero ph-noise model- 2Gbps 16QAM,- Roll-off factor (r) = 0.5- No FEC, AWGN
Eb/N0
BER
pole frequency fp = 1MHzzero frequency fz = 100MHz
Fig.1: Impact of phase-noise at low frequency on 16QAM transmission
- Phase-noise also affects the system performance, significantly.- What values are we going to use for PHY simulation?
-96dBc/Hz-93dBc/Hz-90dBc/Hz-87dBc/Hz
No phase-noise
105 106 107 108 109-160
-150
-140
-130
-120
-110
-100
-90
-80generated phase-noisephase-noise model
Frequency [Hz]
Phas
e-no
ise
[dB
c/H
z]Fig.2: Generated phase-noise based on the model
PSD(0) =-93dBc/Hz
November 2006
Slide 11
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Available 60GHz-band VCO/PLL
- Si-based VCO/PLL is reasonable due to its integrability and power consumption- - 85 – -90dBc/Hz is suitable for low-frequency phase-noise below 1MHz
1.5/2.7V-85 ~ -90dBc/Hz~60GHzSiGe PLL with tripler [5]
3V-90 ~ -95 dBc/Hz~60GHzSiGe:C 0.25um BiCMOS PLL [6]
1.2V-94dBc/Hz 60 GHz0.09um SOI CMOS VCO [4]
1V-110dBc/Hz @ 10MHz offset64 GHz0.09um CMOS VCO [3]
1.5V-89dBc/Hz59 GHz0.13um CMOS VCO [1]
1.5V-85dBc/Hz63 GHz 0.25um CMOS VCO [2]
Supply vol.Phase noise [dBc/Hz] @1MHz offset
Osc. Freq.Fabrication, material
November 2006
Slide 12
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Effect of RF impairment on system performance:HPA, phase-noise, and I/Q imbalance
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Received signal After phase-noiseBefore phase-noise
-1 -0.5 0 0.5 1
-1
-0.5
0
0.5
1
Qua
drat
ure
In-Phase
Received signal After I/Q imbalanceBefore I/Q imbalance
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Received signal After HPABefore HPA
-1 -0.5 0 0.5 1
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
Qua
drat
ure
In-Phase
Received signal
After HPABefore HPA
Power amp. AM-AM effect Power amp. AM-PM effect
Phase-noise I/Q mismatch
(A) (B)
(C) (D)
RF impairment modelconsideration(suggestion)
HPA, phase-noise:mandatory
I/Q mismatch, DAC/ADC:optional
November 2006
Slide 13
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
Conclusion
• Power amplifier and phase-noise model should be considered for accurate PHY evaluation
• Modified Rapp model was suggested for expressing PA nonlinearity
• Phase-noise model was suggested for expressing PLL/VCO
• Reasonable parameters for suggested PA and phase-noise model
Without fixing parameters in proposed model,we cannot match these models to actual 60GHz component measurement results
November 2006
Slide 14
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
References
1. C. Cao, et al., “Millimeter-wave voltage controlled oscillator in 0.13um CMOS technology,” IEEE JSSC, vol. 41, no. 6, Jun. 2006.
2. R.-C. Liu, et al., “A 63GHz VCO using standard 0.25um CMOS process,” IEEE ISSCC 2004.
3. L. M. Franca-Neto, et al.,”64GHz and 100GHz VCO in 90nm CMOS using optimum pumping method,” IEEE ISSCC 2004.
4. F. Ellinger, et al.,”60GHz VCO with wideband tuning range fabricated on VLSI SOI CMOS technology,” IEEE MTT-S, 2004.
5. B. Floyd, et al.,”A silicon 60GHz receiver and transmitter chipset for broadband communications,” IEEE ISSCC 2006.
6. W. Winkler, “A fully integrated BiCMOS PLL for 60GHz wireless applications,” IEEE ISSCC 2005.
November 2006
Slide 15
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
PSD(0) = -100 dBc/Hzpole frequency fp = 250 kHzzero frequency fz = 7905.7 kHzNote, this model results in PSD(infinity) = -130 dBc/HzNote, this impairment is modeled at both transmitter and receiver.
Phase noiseIM4
IEEE 802.11n comparison criteria
Simulation should be run at an oversampling rate of at least 4x. Use RAPP power amplifier model as specified in document 00/294 with p = 3. Calculate backoff as the output power backoff from full saturation: PA Backoff = -10 log10(Average TX Power/Psat).Total TX power shall be limited to no more than 17 dBm.Disclose: (a) EIRP and how it was calculated, (b) PA Backoff, and (c) Psat per PA.Note: the intent of this IM is to allow different proposals to choose different output power operating points.Note: the value Psat = 25dBm is recommended.
PA non-linearityIM1
Status of this IMDefinitionNameNumber
The phase noise will be specified with a pole-zero model.
])/(1[])/(1[)0()( 2
2
p
z
ffffPSDfPSD
++
=
Adapted from IEEE 802.11-03/814r31
November 2006
Slide 16
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
0 100 200 300 400 500 600 700 800 900 10000
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
Degrees
PA
Cur
rent
C lass C PA Current
0 100 200 300 400 500 600 700 800 900 10000
0.2
0.4
0.6
0.8
1
Degrees
PA
Cur
rent
C lass B PA Current
0 100 200 300 400 500 600 700 800 900 10000
0.2
0.4
0.6
0.8
1
Degrees
PA
Cur
rent
C lass AB PA Current
0 100 200 300 400 500 600 700 800 900 10000
0.5
1
1.5
2
Degrees
PA
Cur
rent
C lass A PA Current
Classes of high power amplifier
Class A: Max. power efficiency: 50% Class AB: Max. power efficiency: 50-78%
Class B: Max. power efficiency: 78% Class C: Max. power efficiency: 100%
November 2006
Slide 17
doc.: IEEE 802.15-06-0477-01-003c
Submission Chang-Soon Choi, NiCT
AWGN
f1 f2Phase-noise characteristics
FFT IFFT
freq.
timefreq
timePHASE NOISE FFT
105
106
107
108
109
1010
-170
-160
-150
-140
-130
-120
-110
-100
-90
-80Phase-noiseModel
Frequency offset [Hz]
Phas
e-no
ise
[dB
c/H
z]
How to generate phase-noise
128k FFT point