LED Driver ICs ICL8001G Design Guidelines · η = 90 %, f < fmax = 100 kHz for the input parameters...

Industr ia l & Mult imarket

Appl icat ion Note

Version 1.0, 2010-08-18

ICL8001G Design Guidel inesPhase-Cut-Dimmable Single-Stage LED Driver with PFCusing Quasi-Resonant Primary Power Control

Version 1.0

LED Driver ICs

Edition 2010-08-18Published byInfineon Technologies AG81726 Munich, Germany© 2010 Infineon Technologies AGAll Rights Reserved.

Legal DisclaimerThe information given in this document shall in no event be regarded as a guarantee of conditions or characteristics. With respect to any examples or hints given herein, any typical values stated herein and/or any information regarding the application of the device, Infineon Technologies hereby disclaims any and all warranties and liabilities of any kind, including without limitation, warranties of non-infringement of intellectual property rights of any third party.

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EVAL-LED-ICL8001GDesign Guidelines

Application Note 3 Version 1.0, 2010-08-18

ICL8001G Design Guidelines Revision History: 2010-08-18, Version 1.0Previous Revision: Page Subjects (major changes since last revision)

First edition


Table of Contents


Table of Contents . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4

1 Introduction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5

2 Pin Configuration and Functionality . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 62.1 Pin Configuration with PG-DSO-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 62.2 Package PG-DSO-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 72.3 Pin Functionality . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7

3 Control Principle . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8

4 Design Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 94.1 Transformer Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 94.2 Power Switch . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 104.3 Primary Peak Current Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 114.4 Foldback Correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 124.5 Switch-on Determination for Quasi-resonant Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 134.6 Power Factor Correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 144.7 VCC for Dimming . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14

5 Design Optimizations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 155.1 Dimming . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 155.1.1 Dimming Principle . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 155.1.2 Dimmer Compatibility . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 175.1.3 Dimmer List . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 185.1.4 Dimmer Selection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 195.2 Power Stabilization for Line Voltage Variations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 195.2.1 Stabilization using IC Foldback Correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 195.2.2 Discrete Power Stabilization Circuit . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 205.3 Optimized Power Factor Correction Performance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22

6 Protection Functions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 236.1 Output OVP . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 236.2 Output Short Circuit Protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 236.3 Input Overvoltage Protection (OVP) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23

7 Explicit Questions and Answers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 247.1 Application . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 247.2 Control Principle . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24

8 References . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25

Table of Contents


Introduction

1 Introduction

ObjectiveThe objective of this application note is to describe how a dimmable, highly efficient single-stage LED driver based on the ICL8001G primary control developed by Infineon Technologies AG can be designed and how different design targets can be considered. For this purpose, quantitative design tools for dimensioning of the flyback transformer for QR (quasi-resonant) operation and further discrete components relevant to the power factor correction (PFC) and dimming control functions are provided. The design process refers to a concrete application example of a phase cut dimmable LED driver. Explicit questions and answers are treated in conclusion.

Features of ICL8001G control• High, stable efficiency over a wide operating range• Optimized for trailing and leading-edge dimmers• Precise PWM for primary PFC and dimming control• HV power cell for VCC precharging with a constant current• Built-in digital soft start• Foldback correction and cycle-by-cycle peak current limitation• VCC over/undervoltage lockout• Auto restart mode for short circuit protection• Adjustable latch-off mode for output overvoltage protection (OVP)

DescriptionThe ICL8001G employs a quasi-resonant (QR) operation mode and, due to the availability of outstanding PFC performance, is optimized for off-line LED lighting applications such as dimmable LED bulbs for incandescent lamp replacement, LED downlights and LED tubes in a power range from typically 5 W to 50 W. Precise PWM generation enables primary control for phase cut dimming and potential for high power factors of PF > 99 %. Depending on the power class, significantly improved driver efficiency of up to 91 % is feasible. The product has a wide operation range of IC voltage supply and low power consumption. Multiple safety functions ensure full system protection in failure situations. With its full feature set and simple application, the ICL8001G represents an outstanding choice for QR flyback designs combining feature set and performance at a minimum BOM cost.



Pin Configuration and Functionality

Application circuitFigure 1 below shows the application circuit for the ICL8001G.

Figure 1 ICL8001G application circuit

2 Pin Configuration and Functionality

2.1 Pin Configuration with PG-DSO-8

Table 1 Pin Configuration for PG-DSO-8 Pin Symbol Function1 ZCV Zero Crossing2 VR Voltage Sense3 CS Current Sense4 GD Gate Drive Output5 HV High Voltage Input6 n.c. Not connected7 VCC Controller Supply Voltage8 GND Controller Ground

Cx

Cin

Rn

Cn

Dn

Cvcc

Dvcc

Rs

Do Co

L1 Rvcc

VCC

GND

T1

np

na

ns

Rzc1

Rzc2

ZCV

ICL8001G

Vo

Vac BR Czc

VR

PWM-ControlProtectionGate Driver

Start-Up Cell

Vm( Vs )

Cc

CS

Ro

Ru

NC

HV

GD

DR

Q1

CRRv

L2

Rc

U1

Vin



Pin Configuration and Functionality

2.2 Package PG-DSO-8

Figure 2 Pin Configuration of PG-DSO-8 (top view)

2.3 Pin Functionality

ZCV (Zero Crossing)The voltage from the auxiliary winding after a time delay circuit is applied at this pin. Internally, the pin is connected to the zero-crossing detector for switch-on determination. Additionally, the output overvoltage detection is realized by comparing the voltage Vzc with an internal preset threshold.

VR (Voltage Sense)The rectified input mains voltage is sensed at this pin. The signal is used to set the peak current of the peak-current control and therefore enable the PFC and phase-cut dimming functionality.

CS (Current Sense)This pin is connected to the shunt resistor for the primary current sensing, externally, and to the PWM signal generator for switch-off determination (together with the feedback voltage), internally. Moreover, short-winding protection is realized by monitoring the voltage Vcs during on-time of the main power switch.

GD (Gate Drive Output)This output signal drives the external main power switch, which is a power MOSFET in most cases.

HV (High Voltage)The HV pin is connected to the bus voltage, externally, and to the power cell, internally. The current through this pin precharges the VCC capacitor with a constant current once the supply bus voltage is applied.

VCC (Power supply)The VCC pin is the positive supply of the IC. The operating range is between VVCCoff and VVCCOVP.

GND (Ground)This is the common ground of the controller.

ZCV

VR

CS

GD

GND

VCC

NC

HV

1

2

3

4 5

6

7

8



Control Principle

3 Control Principle

Figure 3 Block diagram of the ICL8001G

An inspection of the ICL8001G block diagram shows that the voltage measured at the shunt resistor Rs (see also the application circuit in Figure 1), which varies according to the instant transformer primary current Ip(t), determines the gain voltage VG as

(1)

With the PWM OP gain GPWM and the offset voltage ram VPWM VG is compared to the voltage VR, which is derived from the input voltage divider (Ro, Ru). This means that the peak current through the power switch Q1 and the primary inductance L varies according to the instant input voltage Vin(t) as expressed by

(2)

Depl. CoolMOS®

Startup CellPower ManagmentZero Crossing

PWM Control

Gate Drive

Protection

GND

GDGate Control

Voltage Reference& Biasing

Over / Under-Voltage Lockout

OTP

Restart / LatchupControl

CSLeading

Edge Blanking

VR

ZCVZero

CurrentDetection

Over Voltage

Protection

PM / PFC Control

FoldbackCorrection

Short Winding

Detection

VG ( Vs )

PWM Comparator

VREF

VFB 25k

2pF

PWMsPWM VRtIpGtIpVG += )())((

RsGtVin

RuRoRutIp

PWM

)()(+

≈



Design Parameters

It can be seen in the non-dimming case that a sinusoidal waveform of the primary peak current is dominant, which defines the almost sinusoidal shape of the input current Iin(t). Beside the PFC function Equation (2) above shows that during phase cut dimming the input current will follow the phase cut-modified input voltage, which assures the dependence of the driver output power on the RMS input voltage Vrms according to the law described by Equation (24) on page 15.

4 Design ParametersThis chapter presents the essential design process and illustrates it in parallel with concrete values which are considered for a sample design with the main target magnitudes VLED = 27 V, ILED = 360 mA, PF = 98 %, η = 90 %, f < fmax = 100 kHz for the input parameters Vin = 230 V, fin = 50 Hz and Pin = VLED ILED / (η PF). The values chosen for the 10 W/230 V LED driver demo board are close to the following calculation results.

4.1 Transformer ParametersFor QR operation, a sufficiently large reflected voltage from the secondary to the primary side present during the flyback time tf has to be provided. After discharge of the transformer by means of the secondary winding current the energy coupled to the reflected voltage is needed to reduce the input voltage at switch-on instantly in the VDS valley to Vdsmin = Vin - Vr. With the selection of Vdsmin = 0 a value Vr = Vinp, where

(3)

is received according to

(4)

The ratio q = Vr / Vinp with q ≤ 1 determines the maximum input voltage Vinp to be processed with zero-voltage switching. The winding ratio rn = np / ns is then calculated as rn = 12.

(5)

The driver operation frequency f varies over the line voltage phase and reaches its maximum values in the line voltage phase close to the voltage peak Vinp. Consideration of a QR mode condition defines the primary inductance L = 6.1 mH (6.3 mH chosen) based on

(6)

With the selection f = fmax, the equation for the minimum on-time

(7)

yields ton = 5.0 µs and so the minimum duty cycle becomes Dmin = 0.5 as

(8)

VinVinp 2=

minVdsVinpVr −=

VdoVLEDVr r

n +=

22

12

−

⎥⎦⎤

⎢⎣⎡ +=

VrVinp

fPinVinL

VinfPinLton 12

=

VinfPinL

D2

min =



Design Parameters

Now the maximum primary peak current arising in the line phase with Vin = Vinp can be fixed as Ipmaxp = 0.27 A according to

(9)

Assuming a saturation inductance of Bm = 0.4 T and Ae = 20.1 mm2 a minimum number of primary turns of np ≈ 200 (np = 190 chosen) would be obtained.

(10)

The maximum magnetic permeance ALmax = 170 nH is obtained using

(11)

which determines the air gap using the k-factors in

(12)

For the often relevant E16-core, the k-factors are k1 = 42.2 and k2 = –0.701 resulting in s ≈ 0.15 mm. The secondary number of turns is then given by

(13)

By choosing ns = 14 and the centered IC supply voltage Vccc = ( Vccmax + Vccmin ) / 2 = 19 the auxiliary winding number will be na = 10 according to

(14)

4.2 Power SwitchThe maximum voltage VDSmax along the drain-source path of the MOSFET arises during the line phase with Vin = Vinp at the instant just subsequent to switching off the primary current. In this phase the high-frequency oscillation amplitude

(15)

adds to the superposition given by the input voltage and reflected voltage to

(16)

The VDSmax value can be limited by either reducing the QR effect (with q) at the cost of driver efficiency or by damping the oscillation by means of a snubber circuit. These limiting approaches can be compared in terms of

fLPinI pp 2max =

BmAeIL

np ppmaxmin =

2maxnpLAL =

21

9

110max k

kALs ⎥

⎦

⎤⎢⎣

⎡=

nrnpns =

VdoVLEDVccnsna

+=

max

CdsLsIVosc ppmax≅

oscinpDS VqVV ++= )1(max



Design Parameters

cost and efficiency reduction with the option of choosing MOSFETs with higher breakdown voltages. For high efficiency it is recommended to make the adjustment VDSmax = 2 Vinp + Vosc < 800 V or 900 V respectively. If necessary, a transformer design with q < 1 (meaning reduced QR operation effect) should be favored over high snubber losses.

4.3 Primary Peak Current ControlThe peak current charging the primary inductance of the transformer reaches its maximum value at the input voltage Vinp. By choosing the maximum threshold Vcsmax = 0.75 V for the shunt voltage generated at the instant of Vinp, the shunt resistance is Rs = 2.7 Ω based on

(17)

The upper resistor, Ro, in the input voltage divider is dimensioned in consideration of losses and PFC. For efficiency optimization, high ohmic values are preferred. A low ohmic input voltage divider enables a maximum power factor adjustment.The resistance of the lower input voltage divider resistor is expressed as

(18)

For the selection Vcsmax ≈ 0.75V and Rs = 2.7 Ω the Ru equation above helps to define (with the specification of Ro = 560 kΩ) a resistance of Ru = 4.3 kΩ (choose Ru = 3.9 kΩ).

ppIVcsRs

max

max=

RsIGVinpIGRsRo

RuppPWM

ppPWM

max

max

−=



Design Parameters

4.4 Foldback CorrectionWhen the line input voltage increases, the comparator threshold for switching off the power switch is reached in a shorter time and the resulting increase in operation frequency would lead to a strong increase in the LED driver power. To limit the input voltage dependence above a certain limit Vinth, the foldback correction reduces the threshold Vcsmax(Icz) in accordance with the current detected at the ZCD pin as expressed here:

(19)

The characteristic curve Vcsmax(Izc) implemented in the IC shows the following steps:

Figure 4 Vcsmax(lzc) characteristic curve

For the adjusted setting Vinth = Vinp and selection of the foldback operation point Vcs-max = 0.75 V / Icz = 1 mA, using the characteristic curve the detection resistance is calculated to be Rzc1 ≈ 15 kΩ according to

(20)

From the characterisitic curve it can be seen that the Vin dependence of Vcsmax is stronger in the range of higher threshold values. This means that if a strong impact of the foldback correction is desired, the Vcs should reach rather high values at Vinp. For increased power constancy under input voltage voltage variations, higher values of R4 and R19 should be chosen.

npna

RczVinVinIcz1

)( =

npna

IczthVinRcz =1



Design Parameters

4.5 Switch-on Determination for Quasi-resonant OperationFor ideal quasi-resonant operation the switch-on of the power switch should occur when the transformer current in the output circuit reaches zero and half of the oscillation period (oscillation 2 in Figure 5) defined by the leakage inductance and the drain-source capacitance of the power switch has elapsed.

Figure 5 Determination of the switch-on instant

The delay td elapses from the instant of discharging the transformer to when the first VDS valley is reached. For initial dimensioning of the delay circuit the relationship

(21)

can be used. For the 230 V / 10 W demo board an initial value of td ≈ 1 µs is appropriate. For output overvoltage protection with final shutdown at Vo > 45 V it turns out to be useful to choose Rzc2 ≈ 2 kΩ. Consequently, the capacitance of the delay circuit Czc = 580 pF (choose Czc = 470 pF) will be obtained according to

(22)

CdsLtd π≅

2121

RzcRzcRzcRzctdCzc +

≅



Design Parameters

4.6 Power Factor CorrectionThe PFC function provides a sinusoidal input current waveform. For this, the setpoint at pin VR should be related strongly to the input voltage waveform Vin(t). The internal reference voltage Vref is connected via the internal resistor VFB to the pin VR. The voltage waveform VR(t) over the line period can be influenced in such a way that a more trapezoidal curve is generated and the input current waveform behaves accordingly. An input voltage divider with Ro ≈ 500 kΩ at Vac = 230 V delivers a high power factor of typically PF > 95 % and dissipates low power for high driver efficiency. High PF values above 99 % and low total harmonic distortion of typically 10 % are achievable at decreased power tolerances. If high power factor adjustment has priority, it is also important to select an elevated threshold for foldback correction Vinth ≈ Vinp.

Figure 6 Power factor correction

4.7 VCC for DimmingThe dimming feature is closely coupled to the PF control as the variation of the setpoint VR(t) determines the power flow to the QR-operated flyback. This is also true if the input voltage is shaped by means of a phase cut dimmer, regardless of whether this is a trailing or leading edge wall dimmer. Therefore the variation of the effective input voltage determines the power level supplied to the LED load at the driver output. The low frequency variation of the input power is smoothened by means of an output capacitor Co storing enough energy to cause no visible light flickering.For a stable IC supply voltage at phase cut dimming more severe conditions have to be observed. Extended temporal gaps with zero input voltage, especially at low dimming levels, are present. Also a certain decrease in output voltage is present in the continuous dimming state of the LED. The Vcc capacitor Cvcc can be designed using

(23)

For dimming applications the assumptions of voltage variation ∆VCCdim = 5 V, IVCC = 5 mA and Tgap ≈ 2 x 10 ms for line half-periods with phase cut dimmer malfunction, a Cvcc ≈ 20 µF would be required, while for non-dimming application the capacitance requirement could be half of that value. For dimmable drivers with Cvcc = 22 µF a short time of 300 ms to light can be realized due to the charging current provided by the HV start-up cell.

dimVCCTgapIVCCCvcc

Δ≅



Design Optimizations

5 Design Optimizations

5.1 Dimming

5.1.1 Dimming PrincipleThe LED driver input voltage at phase cut dimming with the switching instant ts will generate an effective voltage of Vineff(ts). From the applied dimming principle it can be seen that the LED power will depend on Vineff(ts) according to the proportionality law

(24)

where 1.5 < x < 2.0. Consequently, the light level depends on the RMS input voltage Vrms(ts) provided by the phase cut dimmer and the dimming range is therefore given by the phase-cut limits of the wall dimmer. For the example of a trailing edge dimmer, the following diagrams show the time dependence of the modified input voltage V(t,ts) with the fixed parameter switching instant ts = T/4 and the RMS input voltage Vrms(ts) during a theoretical full variation of switching instants ts for visualization of the mathematical function Vrms(ts).

Figure 7 Timing dependency on input voltage

Figure 8 Timing dependency on RMS input voltage

xtsVrmstsVrmsPLED ))(())(( ≈




Phase cut dimming arrangement

Figure 9 Phase cut dimming arrangement

The experimental dependence PLED(Vrms) is illustrated using a 40 Weq LED bulb driver controlled with a trailing edge phase cut dimmer.

Figure 10 Output power versus input trail edge Vrms

Effective for the application is the dependence of the LED driver power on the switching instant ts / switching angle. The following experimental diagram obtained with an Ehmann trailing edge dimmer shows the dependence of the switching instant ts on the driver input power (upper curve) and LED power (lower curve) respectively.

Figure 11 Relationship between switch-off instant ts and power

Phase Cut DimmerICL8001G

LED DriverLED Array

Vac +

_Vac VLED

+

_




The lower curve corresponds closely to the lumen flux of the LED array supplied by the driver and illustrates a continuous increase for the switching angle variation at the wall dimmer.

5.1.2 Dimmer CompatibilityThe driver operation with TRIAC dimmers makes it necessary to observe the requirements regarding their hold-up currents. In addition, the steep rising voltage slopes can excitate disturbing interactions with the parasitics of the EMI filter of the driver. To dampen these interactions it is useful to implement a low-pass filter close to the EMI filter. As placement of the filter in front of the input rectifier would decrease the EMI filter performance it is recommendable to choose a position parallel to the input voltage divider. In the circuit diagram further below, an R-C circuit is implemented. Dimensioning of R8 = 220 Ω and C8 = 68 nF (not integrated in the standard demo board layout) provides stabilization for leading-edge dimmer operation. The non-dimming driver efficiency is reduced by only typically 1 %.

Figure 12 Extended application circuit for dimming

Especially for applications with low input voltage and resulting higher input currents, shaping of the input current waveforms has been shown to be effective in achieving dimming stability. For this, an increase in the ratio R17 / (R17+ R19) and increase in R4 for keeping the LED power constant is suggested. The principal modification of the modification on the different waveforms is indicated in Figure 13 below.

C1

C11

R1

C12

D5

C15

D6

R4

D21 C25

L1 R2

VCC

GND

T1

np

na

ns

R6R3

ZCV

ICL8001G

VLED

Vac BR1

C18

VR

PWM-ControlProtectionGate Driver

Start-Up Cell

Continuous Mode DIM Control

PFC

C5

CS

R19

R17

NC

HV

GD

D7

Q1

C17R5

L2

R7

Vin

C8

R8

5

3

1

2

6

8




Figure 13 Input current waveforms

For an input supply voltage of 100 V the resistors have been changed accordingly: R19 from 3.9 kΩ to 10 kΩ, R19 from 150 kΩ to 300 kΩ and R4 from 2.2 Ω to 2.7 Ω. The increased dimmer compatibility decreases the power factor from 99 % to 86 %. This modification can be combined with dimensioning for a stronger effect of the foldback correction. Designs with an increased VR voltage level will lead to a reduction in driver efficiency.

5.1.3 Dimmer List

Table 2 Input voltage 230 V / 10 W Manufacturer Type/designation Power limit Dimming rangePDL Leading Edge CAT634LM 450 W 20 – 100 %Busch Leading Edge 2200 400 W 16 – 100 %Ehmann Leading Edge T10 300 W 3 – 100 %Ehmann Trailing Edge T46 315 W 23 – 100 %HPM Trailing Edge Cat400T 400 W 6 – 100 %PDL Trailing Edge CAT624TM 450 W 10 – 100 %

Table 3 Input voltage 100 V / 10 W Manufacturer Type/designation Power limit Dimming rangeLEVITON Leading Edge decora RPI06 600 W 11 – 100 %LEVITON Leading Edge TRIMATRON 6684 600 W 5 – 100 %LUTRON Leading Edge SKYLARK S-600H-WH 600 W 3 – 100 %LUTRON Leading Edge SKYLARK S-600P 600 W 4 – 100 %LUTRON Leading Edge TOGGLER TG-600PH-IV 600 W 9 – 100 %




5.1.4 Dimmer SelectionWith ICL8001G control the LED driver can be operated without a wall dimmer as well as using trailing- and leading-edge dimmers. With the phase-cut dimmers applied above, a satisfying light quality and variation in the LED lumen flux over the dimming range has been achieved. For both technologies the phase-cut range should be sufficiently large to provide the dimming range required. The dimming range available with a particular dimmer for incandescent lamps is directly transferred to the LED driver with ICL8001G, but the lumen output of the LEDs at the minimum dimming position will be higher than with incandescent lamps as they need a high amount of thermal power to enable the visible light radiation process. Particularly for operation with 230 V input voltage, leading-edge wall dimmers with a lower rated power range – and hence lower hold-up current requirements – should be selected in order to prevent the occurrence of repetitive TRIAC ignition. Operation with lower input voltages, such as 110 V, provides a higher input current, which in principle supports more stable TRIAC operation.Touch dimmers with internal IC control, which depends exclusively on a resistive load for sufficient digital IC supply, should not be selected for LED driver control.

5.2 Power Stabilization for Line Voltage VariationsFor stable lumen output and limitation of LED power during mains voltage variations it may be useful to consider power stabilization for the LED driver design. This can be achieved by appropriate use of IC foldback correction without additional external components.

5.2.1 Stabilization using IC Foldback CorrectionDriver design can be dimensioned in such a way that PLED variation becomes smaller in the range Vin,min < Vin < Vin,max than would be expected from the approximate quadratic power law. The effect of the foldback correction on LED power and LED current variations can be enhanced by means of an increased R17 value with a constant R19. This will modify the input current waveform from sinusoidal to a more rectangular curve. The LED power can be readjusted by means of the shunt resistor R4. The effect of the foldback correction on the LED power and on LED current variation can be further increased by additionally lowering the Vcs limit. For this second step the R6 value is decreased.PLED is readjusted using the shunt resistor R4. The R6 value can be decreased until the latch-off threshold of the output overvoltage detection is reached. The principal experimental LED current increase for a 10 % input voltage increase is shown in the following diagram. For input voltage drops, similar behavior is obtained for the LED current decrease.




Figure 14 LED current behavior according to power factor using foldback correction

The table below shows the relevant design parameters. Consideration of EMI and driver efficiency designs with PF > 90 % are recommended.

The LED driver should be designed for operation at the maximum voltage arising in the input voltage range.

5.2.2 Discrete Power Stabilization CircuitFor especially high requirements regarding input power or LED current stability for line voltage variations, such as ∆ILED ≤ +/- 2 % at ∆Vac = +/- 10 %, and for low harmonic distortion, a solution using a discrete differential amplifier can be proposed. Here the Vin signal is sensed by means of a voltage divider consisting of R21 and R22, and smoothed by C21. The Zener diode D21 is used for the reference voltage. When the smoothed voltage is much smaller than the reference voltage, the current though R23 will flow only through R24 and there is no influence on the output power of the demo board. When the value of the smoothed voltage is near the reference voltage, part of the current flowing through R23 will begin flowing through R25, R26 and R4 to GND to generate an additional voltage drop. Subsequently, its waveform shows the same slope at pin CS as the rectified input voltage Vin(t).

Table 4 Design parameters for stabilization using foldback correction R17 R19 R6 R4 Pin, rel

[%]ILEDrel, dec

[%]ILEDrel, inc

[%]10k 560k 10k 3R3 4.9 3.8 410k 560k 6k8 3R3 6 5 53k9 560k 10k 2R7 12 11.6 10




Figure 15 Discrete power stabilization circuit

As the on-time of the power MOSFET Q1 is reduced the LED driver power is also reduced. The parameters should be adjusted so that the smoothed voltage at the base of Q21 is equal to the reference voltage at the base of Q22 at the nominal input voltage. The maximal additional voltage drop on the CS pin should be approximately 10 % to 20 % of the original CS limit at the maximum input voltage. As the waveform of the additional voltage drop at the CS pin has the same slope as Vin(t), the input current will not change significantly, but still enable designs with a high power factor and low harmonic distortion. Careful optimization of the discrete stabilization circuit containing the components stated in the BOM below when connected to the 230 V / 10 W driver delivers variations of ∆ILED ≤ + 0.3 % and ∆ILED ≤ –1.3 % at ∆Vac = +10 % and ∆Vac = –10 % respectively. There is no influence on output short circuit and output open loop detection.

Figure 16 Bill of Materials (BOM) for power stabilization circuit

Component Value PackageQ21 BC860B (PNP) SOT23Q22 BC860B (PNP) SOT23C21 470nF/50V 0805R21 2.2MΩ 0805R22 75kΩ 0805R23 1MΩ 0805R24 10k 0805R25 10k 0805R26 1k5 0805R27 68k 0805D21 ZMM6V8 Minimelf

BOM of Discrete Power Stabilization Circuit for 230V / 10W ICL8001G LED Driver Demoboard




5.3 Optimized Power Factor Correction PerformanceDriver optimization for high power factor correction can deliver very high PF > 99 % and THD ≈ 10 %. Corresponding measurements for a 100 V / 10 W LED driver result in the timing diagrams for the setpoint voltage VR(t) and driver input current Iin(t).

Figure 17 Optimized power factor correction

Figure 18 Bill of Materials (BOM) for 100 V / 10 W LED driver with high PF



Protection Functions

6 Protection FunctionsThe following ICL8001G protection functions are provided.

6.1 Output OVPBy means of VCC overvoltage detection it is possible to switch to Auto Restart Mode, which causes a blinking effect of the LED. The output voltage threshold Voovp_vcc can be adjusted by means of the resistor Rvcc in the VCC supply circuit.A second output overvoltage threshold Voovpth can be adjusted to set Latched Off Mode using the IC threshold Vzcovp = 3.7 V. For a decreased output OV threshold Voovpth = 35 V the Rzc2 resistance value is increased to Rzc2 = 2.7 kΩ based on the equation

(25)

6.2 Output Short Circuit ProtectionIn the case of an output short circuit, the IC will switch to Auto Restart Mode by means of VCC undervoltage detection. No special dimensioning is required for this purpose.

6.3 Input Overvoltage Protection (OVP)Upon input overvoltage the foldback point correction becomes active and limits the LED driver input power at the thresholds stated above.

Table 5 ICL8001G protection functions VCC Overvoltage Auto Restart ModeVCC Undervoltage Auto Restart ModeOutput Overvoltage Latched Off ModeOutput Short Circuit Auto Restart ModeShort Winding Latched Off ModeOver temperature Auto Restart Mode

vpVzconsVoovpthnavpVzcoRzcnsRzc

−=

12



Explicit Questions and Answers

7 Explicit Questions and Answers

7.1 Application

What are the main applications of ICL8001G Control?ICL8001G is optimized for offline LED lighting like dimmable LED bulbs for incandescent lamp replacement, LED downlights and LED tubes. The PFC function enables a power range of typically 5 W to 50 W to be applied.Should LED drivers for universal input voltage be designed?Universal input designs lead to essential efficiency reduction in the LED driver and are therefore not supported by special IC features.Is it possible to supply different LED modules with strong variations in total forward voltages?The LED driver requirements under strongly varying conditions of phase-cut dimming are tough. The VCC concept compatible with these requirements and proposed here does not allow for strong variations in the DC output voltage but only for limited output voltage variation. Only in this case is a constant transformer winding ratio or a design with single transformer connecting points at the auxiliary winding sufficient. How can driver efficiencies exceeding 90 % be realized?Generally at higher power applications with pin ≈ 15 W, driver efficiencies > 90% can be realized using optimized QR control with ICL8001G.Can we disable the dimming function and use it as a constant current LED driver with a good power factor?TDA 4863-2 is recommended for this kind of application. For details, see the Application Note AN186.What will happen under no-load conditions?The application circuits based on ICL8001G are designed to work with LEDs only. Under no-load conditions it will go to either the auto restart mode due to Vcc OVP or latched off mode due to output OVP.

7.2 Control Principle

How does ICL8001G realize dimming control and power factor correction? Both dimming control and PFC are achieved with the input mains voltage sensing at the VR pin. This signal is used to set the peak current of the primary winding and consequently allows both PFC and phase-cut dimming functionality by regulating the cycle energy.What are the effects of constant power control compared to constant current?Under constant power control, variations in the LED forward voltage may cause certain variations in the lumen output while, in contrast, the output remains approximately unchanged under constant LED current control. However, the power control concept also enables the LEDs to be operated thermally under stable conditions. Combination of output power control with power stabilization under input voltage variation as proposed above makes it possible to optimize the heat sink design of an LED bulb or LED lighting fixture and hence minimize system costs.How does the ICL8001G achieve the regulation of the current through the LEDs?ICL8001G controls the cycle energy stored in the primary inductance of the flyback transformer. When also considering the frequency behavior, the resulting LED power depends on quite a few parameters. The influence of input voltage variation can be reduced with the design means described above. The tolerances of the current sense resistor R4, the voltage dividers formed by R17 and R19 as well as R6 & R3 have also to be considered.



References

The ICL8001G PWM parameter GPWM and offset voltage needed for low driver tolerances possess especially high precision, as stated in the ICL8001G data sheet.

8 References

Data Sheet ICL8001G

AN EVAL-LED-ICL8001G-Bulb02 for LED Drivers 230 V / 10 W

AN186 – 40 W LED Street and Indoor Lighting Reference Design


http://www.infineon.com/dgdl/Application_Note_ICL8001G.pdf?folderId=db3a304316f66ee801178c31a9af054a&fileId=db3a304326dfb1300126f4b3aeac1838

http://www.infineon.com/dgdl/AN186+-+40W+LED+Street+and+Indoor+lighting+demonstrator+board.pdf?folderId=db3a304313b8b5a60113d4239297042f&fileId=db3a304325afd6e0012607f505a17cf6

http://www.infineon.com/dgdl/Datasheet_ICL8001G+vers+1.pdf?folderId=db3a304316f66ee801178c31a9af054a&fileId=db3a3043271faefd01273dce7b0e68f6

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LED Driver ICs ICL8001G Design Guidelines · η = 90 %, f < fmax = 100 kHz for the input parameters...

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